LTC6101/LTC6101HV
1
6101fh
TYPICAL APPLICATION
FEATURES
APPLICATIONS
DESCRIPTION
High Voltage,
High-Side Current Sense
Amplifi er in SOT-23
TO µP
6101 TA01
LTC2433-1
LTC6101HV
ROUT
4.99k
RIN
100
VOUT
V+
V–
OUT
–IN
+IN
VSENSE
ILOAD
5V TO 105V
1µF
5V
L
O
A
D
–+
–
+
VOUT = • VSENSE = 49.9VSENSE
ROUT
RIN
16-Bit Resolution Unidirectional Output into LTC2433 ADC Step Response
5.5V
5V
0.5V
0V
500ns/DIV
6101 TA01b
T
A
= 25°C
V
+
= 12V
R
IN
= 100
R
OUT
= 5k
V
SENSE
+
= V
+
V
OUT
V
SENSE
–
ΔV
SENSE
–
= 100mV
I
OUT
= 100µA
I
OUT
= 0
The LTC
®
6101/LTC6101HV are versatile, high voltage, high
side current sense amplifi ers. Design fl exibility is provided
by the excellent device characteristics; 300V Max offset
and only 375A (typical at 60V) of current consumption.
The LTC6101 operates on supplies from 4V to 60V and
LTC6101HV operates on supplies from 5V to 100V.
The LTC6101 monitors current via the voltage across an
external sense resistor (shunt resistor). Internal circuitry
converts input voltage to output current, allowing for a
small sense signal on a high common mode voltage to
be translated into a ground referenced signal. Low DC
offset allows the use of a small shunt resistor and large
gain-setting resistors. As a result, power loss in the shunt
is reduced.
The wide operating supply range and high accuracy make
the LTC6101 ideal for a large array of applications from
automotive to industrial and power management. A maxi-
mum input sense voltage of 500mV allows a wide range
of currents to be monitored. The fast response makes the
LTC6101 the perfect choice for load current warnings and
shutoff protection control. With very low supply current,
the LTC6101 is suitable for power sensitive applications.
The LTC6101 is available in 5-lead SOT-23 and 8-lead
MSOP packages.
n Current Shunt Measurement
n Battery Monitoring
n Remote Sensing
n Power Management
n Supply Range:
5V to 100V, 105V Absolute Maximum (LTC6101HV)
4V to 60V, 70V Absolute Maximum (LTC6101)
n Low Offset Voltage: 300μV Max
n Fast Response: 1μs Response Time (0V to 2.5V on
a 5V Output Step)
n Gain Confi gurable with 2 Resistors
n Low Input Bias Current: 170nA Max
n PSRR: 118dB Min
n Output Current: 1mA Max
n Low Supply Current: 250A, V
S = 12V
n Specifi ed Temperature Range: –40°C to 125°C
n Operating Temperature Range: –55°C to 125°C
n Low Profi le (1mm) SOT-23 (ThinSOT™) Package
L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks and
ThinSOT is a trademark of Linear Technology Corporation. All other trademarks are the property
of their respective owners.
LTC6101/LTC6101HV
2
6101fh
ABSOLUTE MAXIMUM RATINGS
ORDER INFORMATION
Total Supply Voltage (V+ to V–)
LTC6101 ............................................................... 70V
LTC6101HV ........................................................ 105V
Minimum Input Voltage (–IN Pin) .................... (V+ – 4V)
Maximum Output Voltage (Out Pin) ............................9V
Input Current ....................................................... ±10mA
Output Short-Circuit Duration (to V–) .............. Indefi nite
Operating Temperature Range
LTC6101C/LTC6101HVC .......................– 40°C to 85°C
LTC6101I/LTC6101HVI ......................... –40°C to 85°C
LTC6101H/LTC6101HVH ................... –55°C to 125°C
Specifi ed Temperature Range (Note 2)
LTC6101C/LTC6101HVC ........................... 0°C to 70°C
LTC6101I/LTC6101HVI ......................... –40°C to 85°C
LTC6101H/LTC6101HVH ................... –40°C to 125°C
Storage Temperature Range .................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec) ................. 300°C
(Note 1)
PIN CONFIGURATION
LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE
LTC6101ACMS8#PBF LTC6101ACMS8#TRPBF LTBSB 8-Lead Plastic MSOP 0°C to 70°C
LTC6101AIMS8#PBF LTC6101AIMS8#TRPBF LTBSB 8-Lead Plastic MSOP –40°C to 85°C
LTC6101AHMS8#PBF LTC6101AHMS8#TRPBF LTBSB 8-Lead Plastic MSOP –40°C to 125°C
LTC6101HVACMS8#PBF LTC6101HVACMS8#TRPBF LTBSX 8-Lead Plastic MSOP 0°C to 70°C
LTC6101HVAIMS8#PBF LTC6101HVAIMS8#TRPBF LTBSX 8-Lead Plastic MSOP –40°C to 85°C
LTC6101HVAHMS8#PBF LTC6101HVAHMS8#TRPBF LTBSX 8-Lead Plastic MSOP –40°C to 125°C
1
2
3
4
–IN
NC
NC
OUT
8
7
6
5
+IN
V+
NC
V–
TOP VIEW
MS8 PACKAGE
8-LEAD PLASTIC MSOP
TJMAX = 150°C, θJA = 300°C/ W
OUT 1
V– 2
TOP VIEW
S5 PACKAGE
5-LEAD PLASTIC TSOT-23
–IN 3
5 V+
4 +IN
TJMAX = 150°C, θJA = 250°C/ W
LTC6101/LTC6101HV
3
6101fh
ORDER INFORMATION
Lead Free Finish
TAPE AND REEL (MINI) TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE
LTC6101ACS5#TRMPBF LTC6101ACS5#TRPBF LTBND 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101AIS5#TRMPBF LTC6101AIS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101AHS5#TRMPBF LTC6101AHS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101BCS5#TRMPBF LTC6101BCS5#TRPBF LTBND 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101BIS5#TRMPBF LTC6101BIS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101BHS5#TRMPBF LTC6101BHS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101CCS5#TRMPBF LTC6101CCS5#TRPBF LTBND 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101CIS5#TRMPBF LTC6101CIS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101CHS5#TRMPBF LTC6101CHS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101HVACS5#TRMPBF LTC6101HVACS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101HVAIS5#TRMPBF LTC6101HVAIS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101HVAHS5#TRMPBF LTC6101HVAHS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101HVBCS5#TRMPBF LTC6101HVBCS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101HVBIS5#TRMPBF LTC6101HVBIS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101HVBHS5#TRMPBF LTC6101HVBHS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101HVCCS5#TRMPBF LTC6101HVCCS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101HVCIS5#TRMPBF LTC6101HVCIS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101HVCHS5#TRMPBF LTC6101HVCHS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 125°C
TRM = 500 pieces. *Temperature grades are identifi ed by a label on the shipping container.
Consult LTC Marketing for parts specifi ed with wider operating temperature ranges.
Consult LTC Marketing for information on lead based fi nish parts.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifi cations, go to: http://www.linear.com/tapeandreel/
LTC6101/LTC6101HV
4
6101fh
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
VSSupply Voltage Range ●460V
VOS Input Offset Voltage VSENSE = 5mV, Gain = 100, LTC6101A
VSENSE = 5mV, Gain = 100, LTC6101AC, LTC6101AI
VSENSE = 5mV, Gain = 100, LTC6101AH
●
●
±85 ±300
±450
±535
µV
µV
µV
VSENSE = 5mV, Gain = 100, LTC6101B
●
±150 ±450
±810
µV
µV
VSENSE = 5mV, Gain = 100, LTC6101C
●
±400 800
1200
µV
µV
∆VOS/∆T Input Offset Voltage Drift VSENSE = 5mV, LTC6101A
VSENSE = 5mV, LTC6101B
VSENSE = 5mV, LTC6101C
●
●
●
±1
±3
±5
µV/°C
µV/°C
µV/°C
IBInput Bias Current RIN = 1M
●
100 170
245
nA
nA
IOS Input Offset Current RIN = 1M ●±2 ±15 nA
VSENSE(MAX) Input Sense Voltage Full Scale VOS within Specifi cation, RIN = 1k (Note 3) ●500 mV
PSRR Power Supply Rejection Ratio VS = 6V to 60V, VSENSE = 5mV, Gain = 100
●
118
115
140 dB
dB
VS = 4V to 60V, VSENSE = 5mV, Gain = 100
●
110
105
133 dB
dB
VOUT Maximum Output Voltage 12V ≤ VS ≤ 60V, VSENSE = 88mV
VS = 6V, VSENSE = 330mV, RIN = 1k, ROUT = 10k
VS = 4V, VSENSE = 550mV, RIN = 1k, ROUT = 2k
●
●
●
8
3
1
V
V
V
VOUT (0) Minimum Output Voltage VSENSE = 0V, Gain = 100, LTC6101A
VSENSE = 0V, Gain = 100, LTC6101AC, LTC6101AI
VSENSE = 0V, Gain = 100, LTC6101AH
●
●
030
45
53.5
mV
mV
mV
VSENSE = 0V, Gain = 100, LTC6101B
●
045
81
mV
mV
VSENSE = 0V, Gain = 100, LTC6101C
●
0150
250
mV
mV
IOUT Maximum Output Current 6V ≤ VS ≤ 60V, ROUT = 2k, VSENSE = 110mV, Gain = 20
VS = 4V, VSENSE = 550mV, Gain = 2, ROUT = 2k
●
●
1
0.5
mA
mA
trInput Step Response
(to 2.5V on a 5V Output Step)
∆VSENSE = 100mV Transient, 6V ≤ VS ≤ 60V, Gain = 50
VS = 4V
1
1.5
µs
µs
BW Signal Bandwidth IOUT = 200A, RIN = 100, ROUT = 5k
IOUT = 1mA, RIN = 100, ROUT = 5k
140
200
kHz
kHz
ISSupply Current VS = 4V, IOUT = 0, RIN = 1M
●
220 450
475
µA
µA
VS = 6V, IOUT = 0, RIN = 1M
●
240 475
525
µA
µA
VS = 12V, IOUT = 0, RIN = 1M
●
250 500
590
µA
µA
VS = 60V, IOUT = 0, RIN = 1M
LTC6101AI, LTC6101AC, LTC6101BI, LTC6101BC,
LTC6101CI, LTC6101CC
LTC6101AH, LTC6101BH, LTC6101CH
●
●
375 640
690
720
µA
µA
µA
ELECTRICAL CHARACTERISTICS
(LTC6101) The ● denotes the specifi cations which apply over the full
specifi ed temperature range, otherwise specifi cations are at TA = 25°C, RIN = 100Ω, ROUT = 10k, VSENSE+ = V+ (see Figure 1 for
details), 4V ≤ VS ≤ 60V unless otherwise noted.
LTC6101/LTC6101HV
5
6101fh
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
VSSupply Voltage Range ●5 100 V
VOS Input Offset Voltage VSENSE = 5mV, Gain = 100, LTC6101HVA
VSENSE = 5mV, Gain = 100, LTC6101HVAC, LTC6101HVAI
VSENSE = 5mV, Gain = 100, LTC6101HVAH
●
●
±85 ±300
±450
±535
µV
µV
µV
VSENSE = 5mV, Gain = 100, LTC6101HVB
●
±150 ±450
±810
µV
µV
VSENSE = 5mV, Gain = 100, LTC6101HVC
●
±400 800
1200
µV
µV
∆VOS/∆T Input Offset Voltage Drift VSENSE = 5mV, LTC6101HVA
VSENSE = 5mV, LTC6101HVB
VSENSE = 5mV, LTC6101HVC
●
●
●
±1
±3
±5
µV/°C
µV/°C
µV/°C
IBInput Bias Current RIN = 1M
●
100 170
245
nA
nA
IOS Input Offset Current RIN = 1M ●±2 ±15 nA
VSENSE(MAX) Input Sense Voltage Full Scale VOS within Specifi cation, RIN = 1k (Note 3) ●500 mV
PSRR Power Supply Rejection Ratio VS = 6V to 100V, VSENSE = 5mV, Gain = 100
●
118
115
140 dB
dB
VS = 5V to 100V, VSENSE = 5mV, Gain = 100
●
110
105
133 dB
dB
VOUT Maximum Output Voltage 12V ≤ VS ≤ 100V, VSENSE = 88mV
VS = 5V, VSENSE = 330mV, RIN = 1k, ROUT = 10k
●
●
8
3
V
V
VOUT (0) Minimum Output Voltage VSENSE = 0V, Gain = 100, LTC6101HVA
VSENSE = 0V, Gain = 100, LTC6101HVAC, LTC6101HVAI
VSENSE = 0V, Gain = 100, LTC6101HVAH
●
●
030
45
53.5
mV
mV
mV
VSENSE = 0V, Gain = 100, LTC6101HVB
●
045
81
mV
mV
VSENSE = 0V, Gain = 100, LTC6101HVC
●
0 150
250
mV
mV
IOUT Maximum Output Current 5V ≤ VS ≤ 100V, ROUT = 2k, VSENSE = 110mV, Gain = 20 ● 1 mA
trInput Step Response
(to 2.5V on a 5V Output Step)
∆VSENSE = 100mV Transient, 6V ≤ VS ≤ 100V, Gain = 50
VS = 5V
1
1.5
µs
µs
BW Signal Bandwidth IOUT = 200A, RIN = 100, ROUT = 5k
IOUT = 1mA, RIN = 100, ROUT = 5k
140
200
kHz
kHz
ISSupply Current VS = 5V, IOUT = 0, RIN = 1M
●
200 450
475
µA
µA
VS = 6V, IOUT = 0, RIN = 1M
●
220 475
525
µA
µA
VS = 12V, IOUT = 0, RIN = 1M
●
230 500
590
µA
µA
VS = 60V, IOUT = 0, RIN = 1M
LTC6101HVI, LTC6101HVC
LTC6101HVH
●
●
350 640
690
720
µA
µA
µA
VS = 100V, IOUT = 0, RIN = 1M
LTC6101HVAI, LTC6101HVAC, LTC6101HVBI,
LTC6101HVBC, LTC6101HVCI, LTC6101HVCC
LTC6101HVAH, LTC6101HVBH, LTC6101HVCH
●
●
350 640
690
720
µA
µA
µA
ELECTRICAL CHARACTERISTICS
(LTC6101HV) The ● denotes the specifi cations which apply over the full
specifi ed temperature range, otherwise specifi cations are at TA = 25°C, RIN = 100Ω, ROUT = 10k, VSENSE+ = V+ (see Figure 1 for
details), 5V ≤ VS ≤ 100V unless otherwise noted.
LTC6101/LTC6101HV
6
6101fh
TYPICAL PERFORMANCE CHARACTERISTICS
ELECTRICAL CHARACTERISTICS
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: The LTC6101C/LTC6101HVC are guaranteed to meet specifi ed
performance from 0°C to 70°C. The LTC6101C/LTC6101HVC are designed,
characterized and expected to meet specifi ed performance from –40°C to
85°C but are not tested or QA sampled at these temperatures. LTC6101I/
LTC6101HVI are guaranteed to meet specifi ed performance from –40°C
to 85°C. The LTC6101H/LTC6101HVH are guaranteed to meet specifi ed
performance from –40°C to 125°C.
Note 3: ROUT = 10k for 6V ≤ VS ≤ 100V, ROUT = 2k for VS = 4V.
LTC6101: IOUT Maximum
vs Temperature
Input VOS vs Temperature Input VOS vs Supply Voltage Input Sense Range
LTC6101: VOUT Maximum
vs Temperature
LTC6101HV: VOUT Maximum
vs Temperature
44010 20 30 50 10060 70 80 90
V
SUPPLY
(V)
MAXIMUM V
SENSE
(V)
2.5
2
1.5
1
0.5
0
6101 G05
T
A
= 125°C
T
A
= 85°C
T
A
= 70°C
T
A
= 0°C T
A
= –40°C
R
IN
= 3k
R
OUT
= 3k
T
A
= 25°C
LTC6101
LTC6101HV
TEMPERATURE (°C)
12
10
8
6
4
2
0
–40 40 80 120100–20
6101 G06
020 60
MAXIMUM OUTPUT (V)
VS = 60V
VS = 12V
VS = 6V
VS = 4V
TEMPERATURE (°C)
7
6
5
4
3
2
1
0
–40 40 80 120100–20
6101 G07
020 60
MAXIMUM IOUT (mA)
VS = 12V
VS = 60V
VS = 6V
VS = 4V
INPUT OFFSET (µV)
800
600
400
200
0
–200
–400
–600
–800
–1000
6101 G01
TEMPERATURE (°C)
–40 12004080
–20 20 60 100
A GRADE
B GRADE
C GRADE
RIN = 100
ROUT = 5k
VIN = 5mV
REPRESENTATIVE
UNITS
TEMPERATURE (°C)
12
10
8
6
4
2
0
–40 40 80 120100–20
6101 G20
020 60
MAXIMUM OUTPUT (V)
V
S
= 100V
V
S
= 12V
V
S
= 5V
V
S
= 6V
V
S
= 4V
VSUPPLY (V)
40
20
0
–20
–40
–60
–80
–100
–120
–140
6101 G02
43211 18 25 39 46 53 60
INPUT OFFSET (µV)
RIN = 100
ROUT = 5k
VIN = 5mV TA = 125°C
TA = 85°C
TA = 25°C
TA = –40°C
TA = 0°C
LTC6101/LTC6101HV
7
6101fh
TYPICAL PERFORMANCE CHARACTERISTICS
SUPPLY VOLTAGE (V)
0
SUPPLY CURRENT (µA)
450
400
350
300
250
200
150
100
50
0
32
6101 G11
816 48 56
24 40
28
412 44 52
20 36 60
–40°C
0°C
25°C
70°C
85°C
125°C
V
IN
= 0
R
IN
= 1M
V+
V+-10mV
0.5V
0V
TIME (10µs/DIV)
6101 G12
T
A
= 25°C
V+ = 12V
R
IN
= 100
R
OUT
= 5k
V
SENSE
+ = V+
V
SENSE
–
V
OUT
LTC6101: Supply Current
vs Supply Voltage
Step Response 0mV to 10mV Step Response 10mV to 20mV
Input Bias Current
vs Temperature
Gain vs Frequency
GAIN (dB)
FREQUENCY (Hz)
1k
40
35
30
25
20
15
10
5
0
–5
–10 10k 100k 1M
6101 G09
T
A
= 25°C
R
IN
= 100
R
OUT
= 4.99k
I
OUT = 200µA
I
OUT = 1mA
TEMPERATURE (°C)
160
140
120
100
80
60
40
20
0
–40 40 80 120100–20
6101 G10
020 60
IB (nA)
VS = 6V TO 100V
VS = 4V
Output Error Due to Input Offset
vs Input Voltage
LTC6101HV: IOUT Maximum
vs Temperature
INPUT VOLTAGE (V)
0.1
OUTPUT ERROR (%)
1
10
100
0 0.2 0.3 0.4
0.01
0.1 0.50.15 0.25 0.350.05 0.45
6101 G08
C GRADE
B GRADE
A GRADE
TA = 25°C
GAIN =10
TEMPERATURE (°C)
7
6
5
4
3
2
1
0
–40 40 80 120100–20
6101 G21
020 60
MAXIMUM I
OUT
(mA)
V
S
= 12V
V
S
= 100V
V
S
= 6V
V
S
= 5V
V
S
= 4V
LTC6101HV: Supply Current
vs Supply Voltage
SUPPLY VOLTAGE (V)
0
SUPPLY CURRENT (µA)
600
500
400
300
200
100
0
6101 G22
60
10 3020 40 80 90
50 70 100
–40°C 0°C
85°C
125°C
V
IN
= 0
R
IN
= 1M
70°C
25°C
LTC6101/LTC6101HV
8
6101fh
TYPICAL PERFORMANCE CHARACTERISTICS
FREQUENCY (Hz)
PSRR (dB)
0.1 1 10 100 1k 10k 100k 1M
6101 G19
160
140
120
100
80
60
40
20
0
RIN = 100
ROUT = 10k
COUT = 5pF
GAIN = 100
IOUTDC = 100µA
VINAC = 50mVp
LTC6101HV,
V+ = 5V
LTC6101,
LTC6101HV,
V+ = 12V
LTC6101,
V+ = 4V
V
+
V
+
-100mV
5V
0V
TIME (10µs/DIV)
6101 G14
VOUT
CLOAD = 1000pF
CLOAD = 10pF
VSENSE
–
TA = 25°C
V
+
= 12V
RIN = 100
ROUT = 5k
VSENSE
+
= V
+
V
+
V
+
-100mV
5V
0V
TIME (100µs/DIV)
6101 G15
VOUT
VSENSE
–
TA = 25°C
V
+
= 12V
CLOAD = 2200pF
RIN = 100
ROUT = 5k
VSENSE
+
= V
+
5.5V
5V
0.5V
0V
TIME (500ns/DIV)
6101 G16
V
OUT
V
SENSE–
ΔV
SENSE–
=100mV
I
OUT
= 100µA
I
OUT
= 0
T
A
= 25°C
V
+
= 12V
R
IN
= 100
R
OUT
= 5k
V
SENSE+
= V
+
5.5V
5V
0.5V
0V
TIME (500ns/DIV)
6101 G17
VOUT
ΔVSENSE
–
=100mV
IOUT = 100µ
IOUT = 0
TA = 25°C
V
+
= 12V
RIN = 100
ROUT = 5k
VSENSE
+
= V
+
Step Response Falling Edge
Step Response 100mV Step Response 100mV Step Response Rising Edge
PSRR vs Frequency
LTC6101/LTC6101HV
9
6101fh
BLOCK DIAGRAM
OUT: Current Output. OUT will source a current that is
proportional to the sense voltage into an external resistor.
V–: Negative Supply (or Ground for Single-Supply
Operation).
–IN: The internal sense amplifi er will drive IN– to the same
potential as IN+. A resistor (RIN) tied from V+ to IN– sets
the output current IOUT = VSENSE/RIN. VSENSE is the voltage
developed across the external RSENSE (Figure 1).
+IN: Must be tied to the system load end of the sense
resistor, either directly or through a resistor.
V+: Positive Supply Pin. Supply current is drawn through
this pin. The circuit may be confi gured so that the
LTC6101 supply current is or is not monitored along
with the system load current. To monitor only system
load current, connect V+ to the more positive side of the
sense resistor. To monitor the total current, including the
LTC6101 current, connect V+ to the more negative side
of the sense resistor.
The LTC6101 high side current sense amplifi er (Figure 1)
provides accurate monitoring of current through a user-
selected sense resistor. The sense voltage is amplifi ed by
a user-selected gain and level shifted from the positive
power supply to a ground-referred output. The output
signal is analog and may be used as is or processed with
an output fi lter.
Theory of Operation
An internal sense amplifi er loop forces IN– to have the
same potential as IN+. Connecting an external resis-
tor, RIN, between IN– and V+ forces a potential across
RIN that is the same as the sense voltage across
RSENSE. A corresponding current, VSENSE/RIN, will
fl ow through RIN. The high impedance inputs of the
sense amplifi er will not conduct this input current,
so it will fl ow through an internal MOSFET to the output pin.
The output current can be transformed into a voltage by
adding a resistor from OUT to V–. The output voltage is
then VO = V– + IOUT • ROUT.
–
+
V
+
V
–
10V OUT
6101 BD
LTC6101/LTC6101HV
V
BATTERY
I
OUT
V
SENSE
R
SENSE
I
LOAD
R
OUT
R
IN
–
+
L
O
A
D
V
OUT
= V
SENSE
x R
OUT
R
IN
5k
5k
10V
–IN
+IN
Figure 1. LTC6101/LTC6101HV Block Diagram and Typical Connection
APPLICATIONS INFORMATION
PIN FUNCTIONS
LTC6101/LTC6101HV
10
6101fh
APPLICATIONS INFORMATION
Figure 2. Kelvin Input Connection Preserves
Accuracy Despite Large Load Current
LTC6101
R
OUT
V
OUT
6101 F02
R
IN
V
+
LOAD
R
SENSE
–
+
V
+
V
–
OUT
–IN+IN
Useful Gain Confi gurations
Gain RIN ROUT VSENSE at VOUT = 5V IOUT at VOUT = 5V
20 499 10k 250mV 500µA
50 200 10k 100mV 500µA
100 100 10k 50mV 500µA
Selection of External Current Sense Resistor
The external sense resistor, RSENSE, has a signifi cant effect
on the function of a current sensing system and must be
chosen with care.
First, the power dissipation in the resistor should be
considered. The system load current will cause both heat
and voltage loss in RSENSE. As a result, the sense resis-
tor should be as small as possible while still providing
the input dynamic range required by the measurement.
Note that input dynamic range is the difference between
the maximum input signal and the minimum accurately
reproduced signal, and is limited primarily by input DC
offset of the internal amplifi er of the LTC6101. In addition,
RSENSE must be small enough that VSENSE does not exceed
the maximum input voltage specifi ed by the LTC6101, even
under peak load conditions. As an example, an application
may require that the maximum sense voltage be 100mV.
If this application is expected to draw 2A at peak load,
RSENSE should be no more than 50m.
Once the maximum RSENSE value is determined, the mini-
mum sense resistor value will be set by the resolution or
dynamic range required. The minimum signal that can be
accurately represented by this sense amp is limited by the
input offset. As an example, the LTC6101B has a typical
input offset of 150µV. If the minimum current is 20mA, a
sense resistor of 7.5m will set VSENSE to 150µV. This is
the same value as the input offset. A larger sense resistor
will reduce the error due to offset by increasing the sense
voltage for a given load current.
Choosing a 50m RSENSE will maximize the dynamic range
and provide a system that has 100mV across the sense
resistor at peak load (2A), while input offset causes an
error equivalent to only 3mA of load current.
Peak dissipation is 200mW. If a 5m sense resistor is
employed, then the effective current error is 30mA, while
the peak sense voltage is reduced to 10mV at 2A, dis-
sipating only 20mW.
The low offset and corresponding large dynamic range of
the LTC6101 make it more fl exible than other solutions in
this respect. The 150µV typical offset gives 60dB of dy-
namic range for a sense voltage that is limited to 150mV
max, and over 70dB of dynamic range if the rated input
maximum of 500mV is allowed.
Sense Resistor Connection
Kelvin connection of the IN– and IN+ inputs to the sense
resistor should be used in all but the lowest power ap-
plications. Solder connections and PC board interconnec-
tions that carry high current can cause signifi cant error
in measurement due to their relatively large resistances.
One 10mm x 10mm square trace of one-ounce copper
is approximately 0.5m. A 1mV error can be caused by
as little as 2A fl owing through this small interconnect.
This will cause a 1% error in a 100mV signal. A 10A load
current in the same interconnect will cause a 5% error
for the same 100mV signal. By isolating the sense traces
from the high-current paths, this error can be reduced
by orders of magnitude. A sense resistor with integrated
Kelvin sense terminals will give the best results. Figure 2
illustrates the recommended method.
LTC6101/LTC6101HV
11
6101fh
APPLICATIONS INFORMATION
6101 F03b
–+
–+
–
+
R
5
7.5k
V
IN
301301
V
OUT
I
LOAD
LTC6101
R
SENSE LO
100m
M1
Si4465
10k
CMPZ4697
7.5k
V
IN
1.74M
4.7k
Q1
CMPT5551
40.2k
3
4
5
6
12
8
7
619k
HIGH
RANGE
INDICATOR
(I
LOAD
> 1.2A)
V
LOGIC
(3.3V TO 5V)
LOW CURRENT RANGE OUT
2.5V/A
(
V
LOGIC
+5V
)
≤ V
IN
≤ 60V
0 ≤ I
LOAD
≤ 10A
HIGH CURRENT RANGE OUT
250mV/A
301 301
LTC6101
R
SENSE HI
10m
V
LOGIC
BAT54C
LTC1540
V
+
V
–
OUT
–IN+IN
V
+
V
–
OUT
–IN+IN
Selection of External Input Resistor, RIN
The external input resistor, RIN, controls the transconduc-
tance of the current sense circuit. Since IOUT = VSENSE/RIN,
transconductance gm = 1/RIN. For example, if RIN = 100,
then IOUT = VSENSE/100 or IOUT = 1mA for VSENSE = 100mV.
RIN should be chosen to allow the required resolution
while limiting the output current. At low supply voltage,
IOUT may be as much as 1mA. By setting RIN such that
the largest expected sense voltage gives IOUT = 1mA, then
the maximum output dynamic range is available. Output
dynamic range is limited by both the maximum allowed
output current and the maximum allowed output voltage, as
well as the minimum practical output signal. If less dynamic
range is required, then RIN can be increased accordingly,
reducing the max output current and power dissipation.
If low sense currents must be resolved accurately in a
system that has very wide dynamic range, a smaller RIN
than the max current spec allows may be used if the max
current is limited in another way, such as with a Schottky
diode across RSENSE (Figure 3a). This will reduce the high
current measurement accuracy by limiting the result, while
increasing the low current measurement resolution.
Figure 3b. Dual LTC6101s Allow High-Low Current Ranging
V
+
LOAD
D
SENSE
6101 F03a
R
SENSE
Figure 3a. Shunt Diode Limits Maximum Input Voltage to Allow
Better Low Input Resolution Without Overranging
This approach can be helpful in cases where occasional
large burst currents may be ignored. It can also be used
in a multirange confi guration where a low current circuit
is added to a high current circuit (Figure 3b). Note that
a comparator (LTC1540) is used to select the range, and
transistor M1 limits the voltage across RSENSE LO.
Care should be taken when designing the board layout
for RIN, especially for small RIN values. All trace and inter-
connect impedances will increase the effective RIN value,
causing a gain error. In addition, internal device resistance
will add approximately 0.2 to RIN.
LTC6101/LTC6101HV
12
6101fh
APPLICATIONS INFORMATION
Selection of External Output Resistor, ROUT
The output resistor, ROUT, determines how the output cur-
rent is converted to voltage. VOUT is simply IOUT • ROUT.
In choosing an output resistor, the max output voltage
must fi rst be considered. If the circuit that is driven by
the output does not limit the output voltage, then ROUT
must be chosen such that the max output voltage does
not exceed the LTC6101 max output voltage rating. If the
following circuit is a buffer or ADC with limited input range,
then ROUT must be chosen so that IOUT(MAX) • ROUT is less
than the allowed maximum input range of this circuit.
In addition, the output impedance is determined by ROUT. If
the circuit to be driven has high enough input impedance,
then almost any useful output impedance will be accept-
able. However, if the driven circuit has relatively low input
impedance, or draws spikes of current, such as an ADC
might do, then a lower ROUT value may be required in order
to preserve the accuracy of the output. As an example, if
the input impedance of the driven circuit is 100 times ROUT,
then the accuracy of VOUT will be reduced by 1% since:
VOUT =IOUT •ROUT •R
IN(DRIVEN)
ROUT +RIN(DRIVEN)
=IOUT •ROUT •100
101
=0.99 •IOUT •ROUT
Error Sources
The current sense system uses an amplifi er and resistors
to apply gain and level shift the result. The output is then
dependent on the characteristics of the amplifi er, such as
gain and input offset, as well as resistor matching.
Ideally, the circuit output is:
VOUT =VSENSE •ROUT
RIN
;V
SENSE =RSENSE •ISENSE
In this case, the only error is due to resistor mismatch,
which provides an error in gain only. However, offset
voltage, bias current and fi nite gain in the amplifi er cause
additional errors:
Output Error, EOUT, Due to the Amplifi er DC Offset
Voltage, VOS
E
OUT(VOS) = VOS • (ROUT/RIN)
The DC offset voltage of the amplifi er adds directly to the
value of the sense voltage, VSENSE. This is the dominant
error of the system and it limits the available dynamic
range. The paragraph “Selection of External Current Sense
Resistor” provides details.
Output Error, EOUT, Due to the Bias Currents,
IB(+) and IB(–)
The bias current IB(+) fl ows into the positive input of the
internal op amp. IB(–) fl ows into the negative input.
E
OUT(IBIAS) = ROUT((IB(+) • (RSENSE/RIN) – IB(–))
Since IB(+) ≈ IB(–) = IBIAS, if RSENSE << RIN then,
E
OUT(IBIAS) ≈ –ROUT • IBIAS
For instance if IBIAS is 100nA and ROUT is 1k, the output
error is 0.1mV.
Note that in applications where RSENSE ≈ RIN, IB(+) causes
a voltage offset in RSENSE that cancels the error due to
IB(–) and EOUT(IBIAS) ≈ 0. In applications where RSENSE <
RIN, the bias current error can be similarly reduced if an
external resistor RIN(+) = (RIN – RSENSE) is connected as
shown in Figure 4 below. Under both conditions:
E
OUT(IBIAS) = ± ROUT • IOS; IOS = IB(+) – IB(–)
LTC6101
R
OUT
V
OUT
6101 F04
R
IN
–
V
+
LOAD
R
SENSE
R
IN
+
–
+
R
IN
+
=
R
IN
–
–
R
SENSE
V
+
V
–
OUT
–IN+IN
Figure 4. Second Input R Minimizes
Error Due to Input Bias Current
LTC6101/LTC6101HV
13
6101fh
APPLICATIONS INFORMATION
If the offset current, IOS, of the LTC6101 amplifi er is 2nA,
the 100 microvolt error above is reduced to 2 microvolts.
Adding RIN+ as described will maximize the dynamic
range of the circuit. For less sensitive designs, RIN+ is
not necessary.
Example:
If an ISENSE range = (1A to 1mA) and (VOUT/ISENSE) =
3V/1A
Then, from the Electrical Characteristics of the LTC6101,
RSENSE ≈ VSENSE (max) / ISENSE (max) = 500mV/1A =
500m
Gain = ROUT/RIN = VOUT (max) / VSENSE (max) =
3V/500mV = 6
If the maximum output current, IOUT, is limited to 1mA,
ROUT equals 3V/1mA ≈ 3.01 k (1% value) and RIN =
3k/6 ≈ 499 (1% value).
The output error due to DC offset is ±900µVolts (typ) and
the error due to offset current, IOS is 3k x 2nA = ±6µVolts
(typical), provided RIN+ = RIN–.
The maximum output error can therefore reach ±906µVolts
or 0.03% (–70dB) of the output full scale. Considering
the system input 60dB dynamic range (ISENSE = 1mA to
1A), the 70dB performance of the LTC6101 makes this
application feasible.
Output Error, EOUT, Due to the Finite DC Open Loop
Gain, AOL, of the LTC6101 Amplifi er
This error is inconsequential as the AOL of the LTC6101
is very large.
Output Current Limitations Due to Power Dissipation
The LTC6101 can deliver up to 1mA continuous current to
the output pin. This current fl ows through RIN and enters the
current sense amp via the IN(–) pin. The power dissipated
in the LTC6101 due to the output signal is:
P
OUT = (V–IN – VOUT) • IOUT
Since V–IN ≈ V+, POUT ≈ (V+ – VOUT) • IOUT
There is also power dissipated due to the quiescent sup-
ply current:
P
Q = IDD • V+
The total power dissipated is the output dissipation plus
the quiescent dissipation:
P
TOTAL = POUT + PQ
At maximum supply and maximum output current, the
total power dissipation can exceed 100mW. This will
cause signifi cant heating of the LTC6101 die. In order to
prevent damage to the LTC6101, the maximum expected
dissipation in each application should be calculated. This
number can be multiplied by the θJA value listed in the
package section on page 2 to fi nd the maximum expected
die temperature. This must not be allowed to exceed 150°C,
or performance may be degraded.
As an example, if an LTC6101 in the S5 package is to be
run at 55V ±5V supply with 1mA output current at 80°C:
P
Q(MAX) = IDD(MAX) • V+(MAX) = 41.4mW
P
OUT(MAX) = IOUT • V+(MAX) = 60mW
T
RISE = θJA • PTOTAL(MAX)
T
MAX = TAMBIENT + TRISE
T
MAX must be < 150°C
P
TOTAL(MAX) ≈ 96mW and the max die temp
will be 104°C
If this same circuit must run at 125°C, the max die
temp will increase to 150°C. (Note that supply current,
and therefore PQ, is proportional to temperature. Refer
to Typical Performance Characteristics section.) In this
condition, the maximum output current should be reduced
to avoid device damage. Note that the MSOP package
has a larger θJA than the S5, so additional care must be
taken when operating the LTC6101A/LTC6101HVA at high
temperatures and high output currents.
The LTC6101HV can be used at voltages up to 105V. This
additional voltage requires that more power be dissipated
for a given level of current. This will further limit the allowed
output current at high ambient temperatures.
It is important to note that the LTC6101 has been designed
to provide at least 1mA to the output when required, and
can deliver more depending on the conditions. Care must
be taken to limit the maximum output current by proper
choice of sense resistor and, if input fault conditions exist,
external clamps.
LTC6101/LTC6101HV
14
6101fh
APPLICATIONS INFORMATION
Output Filtering
The output voltage, VOUT, is simply IOUT • ZOUT. This
makes fi ltering straightforward. Any circuit may be used
which generates the required ZOUT to get the desired fi lter
response. For example, a capacitor in parallel with ROUT
will give a low pass response. This will reduce unwanted
noise from the output, and may also be useful as a charge
reservoir to keep the output steady while driving a switch-
ing circuit such as a mux or ADC. This output capacitor
in parallel with an output resistor will create a pole in the
output response at:
f–3dB =1
2•π•ROUT •C
OUT
Useful Equations
Input Voltage: VSENSE =ISENSE •RSENSE
Voltage Gain: VOUT
VSENSE
=ROUT
RIN
Current Gain: IOUT
ISENSE
=RSENSE
RIN
Transconductance: IOUT
VSENSE
=1
RIN
Transimpedance: VOUT
ISENSE
=RSENSE •ROUT
RIN
Figure 5. V+ Powered Separately from
Load Supply (VBATT)
Figure 6. LTC6101 Supply Current
Monitored with Load
LTC6101
ROUT
VOUT
6101 F05
RIN
LOAD V+
RSENSE
VBATTERY
–
+
V+
V–
OUT
–IN+IN
LTC6101
R
OUT
V
OUT
6101 F06
R
IN
LOAD
V
+
R
SENSE
–
+
V
+
V
–
OUT
–IN+IN
Input Common Mode Range
The inputs of the LTC6101 can function from 1.5V below
the positive supply to 0.5V above it. Not only does this
allow a wide VSENSE range, it also allows the input refer-
ence to be separate from the positive supply (Figure 5).
Note that the difference between VBATT and V+ must be no
more than the common mode range listed in the Electrical
Characteristics table. If the maximum VSENSE is less than
500mV, the LTC6101 may monitor its own supply current,
as well as that of the load (Figure 6).
LTC6101/LTC6101HV
15
6101fh
APPLICATIONS INFORMATION
Reverse Supply Protection
Some applications may be tested with reverse-polarity
supplies due to an expectation of this type of fault during
operation. The LTC6101 is not protected internally from
external reversal of supply polarity. To prevent damage that
may occur during this condition, a Schottky diode should
be added in series with V– (Figure 7). This will limit the
reverse current through the LTC6101. Note that this diode
will limit the low voltage performance of the LTC6101 by
effectively reducing the supply voltage to the part by VD.
In addition, if the output of the LTC6101 is wired to a device
that will effectively short it to high voltage (such as through
an ESD protection clamp) during a reverse supply condi-
tion, the LTC6101’s output should be connected through
a resistor or Schottky diode (Figure 8).
Response Time
The LTC6101 is designed to exhibit fast response to inputs
for the purpose of circuit protection or signal transmission.
This response time will be affected by the external circuit
in two ways, delay and speed.
If the output current is very low and an input transient
occurs, there may be an increased delay before the output
voltage begins changing. This can be improved by increas-
ing the minimum output current, either by increasing
RSENSE or decreasing RIN. The effect of increased output
current is illustrated in the step response curves in the
Typical Performance Characteristics section of this data
sheet. Note that the curves are labeled with respect to the
initial output currents.
The speed is also affected by the external circuit. In this
case, if the input changes very quickly, the internal ampli-
fi er will slew the gate of the internal output FET (Figure
1) in order to maintain the internal loop. This results in
current fl owing through RIN and the internal FET. This
current slew rate will be determined by the amplifi er and
FET characteristics as well as the input resistor, RIN. Us-
ing a smaller RIN will allow the output current to increase
more quickly, decreasing the response time at the output.
This will also have the effect of increasing the maximum
output current. Using a larger ROUT will decrease the re-
sponse time, since VOUT = IOUT • ROUT. Reducing RIN and
increasing ROUT will both have the effect of increasing the
voltage gain of the circuit.
Figure 7. Schottky Prevents Damage During Supply Reversal Figure 8. Additional Resistor R3 Protects
Output During Supply Reversal
6101 F07
LTC6101
R2
4.99k
D1
R1
100
VBATT
RSENSE
L
O
A
D
–+
V+
V–
OUT
–IN+IN
6101 F08
ADC
LTC6101
R2
4.99k
D1
R1
100 V
BATT
R3
1k
R
SENSE
L
O
A
D
–+
V
+
V
–
OUT
–IN+IN
LTC6101/LTC6101HV
16
6101fh
TYPICAL APPLICATIONS
Bidirectional Current Sense Circuit with Separate Charge/Discharge Output
LTC6101 Monitors Its Own Supply Current High-Side-Input Transimpedance Amplifi er
L
O
A
D
CHARGER
–+
–+
+
–
+
–
VOUT D = IDISCHARGE • RSENSE
( )
WHEN IDISCHARGE ≥ 0DISCHARGING: ROUT D
RIN D
VOUT C = ICHARGE • RSENSE
( )
WHEN ICHARGE ≥ 0CHARGING: ROUT C
RIN C
6101 TA02
VBATT
RIN C
100
LTC6101
RIN D
100
RIN C
100
LTC6101
VOUT D
ROUT D
4.99k
ROUT C
4.99k
VOUT C
RIN D
100
IDISCHARGE RSENSE ICHARGE
V+
V–
OUT
–IN+IN
V+V–
OUT
–IN +IN
L
O
A
D
–+
6101 TA03
R2
4.99k VOUT
R1
100
VBATT
RSENSE
LTC6101 +
–
VOUT = 49.9 • RSENSE
(
ILOAD + ISUPPLY
)
ILOAD
ISUPPLY
V+
V–
OUT
–IN+IN
–+
6101 TA04
R
L
V
O
4.75k4.75k
V
S
LASER MONITOR
PHOTODIODE
CMPZ4697*
(10V)
10k
i
PD
LTC6101
V
O
= I
PD
•
R
L
*V
Z
SETS PHOTODIODE BIAS
V
Z
+ 4 ≤ V
S
≤ V
Z
+ 60
V
+
V
–
OUT
–IN+IN
LTC6101/LTC6101HV
17
6101fh
TO µP
6101 TA06
LTC2433-1
LTC6101
R
OUT
4.99k
R
IN
100
V
OUT
V
SENSE
I
LOAD
4V TO 60V
1µF
5V
L
O
A
D
–+
–
+
V
OUT
= • V
SENSE
= 49.9V
SENSE
R
OUT
R
IN
ADC FULL-SCALE = 2.5V
21
9
8
7
1063
4
5
V
CC
SCK
REF
+
REF
–
GND
IN
+
IN
–
C
C
F
O
SDD
V
+
V
–
OUT
–IN+IN
16-Bit Resolution Unidirectional Output into LTC2433 ADC
6101 TA07
L
O
A
D
FAULT
OFF ON
15
4.99k
V
O
R
S
3
4
47k
2
8
6
100
100
1%
10µF
63V
1µF
14V
V
LOGIC
SUB85N06-5
V
O
= 49.9 • R
S
• I
L
FOR R
S
= 5m,
V
O
= 2.5V AT I
L
= 10A (FULL SCALE)
LT1910 LTC6101
I
L
V
+
V
–
OUT
–IN
+IN
Intelligent High-Side Switch with Current Monitor
TYPICAL APPLICATIONS
LTC6101/LTC6101HV
18
6101fh
6101 TA08
LTC6101HV
R
IN
V
–
V
–
V
SENSE
R
SENSE
I
SENSE
LOAD
+–
–+
V
OUT
= V
LOGIC –
I
SENSE
• • N • R
OUT
R
SENSE
R
IN
N = OPTOISOLATOR CURRENT GAIN
V
S
ANY OPTOISOLATOR
R
OUT
V
OUT
V
LOGIC
V
+
V
–
OUT
–IN +IN
6101 TA09
LTC6101
RIN
100
VOUT
ROUT
4.99k
L
O
A
D
–+
VOUT = • VSENSE = 49.9 VSENSE
ROUT
RIN
M1 AND M2 ARE FQD3P50 TM
M1
M2
62V
CMZ5944B
500V
2M
VSENSE
RSENSE
ISENSE
+–
DANGER! Lethal Potentials Present — Use Caution
DANGER!!
HIGH VOLTAGE!!
V+
V–
OUT
–IN+IN
48V Supply Current Monitor with Isolated Output with 105V Survivability
Simple 500V Current Monitor
TYPICAL APPLICATIONS
LTC6101/LTC6101HV
19
6101fh
MS8 Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660 Rev F)
MSOP (MS8) 0307 REV F
0.53 ± 0.152
(.021 ± .006)
SEATING
PLANE
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
0.18
(.007)
0.254
(.010)
1.10
(.043)
MAX
0.22 – 0.38
(.009 – .015)
TYP
0.1016 ± 0.0508
(.004 ± .002)
0.86
(.034)
REF
0.65
(.0256)
BSC
0° – 6° TYP
DETAIL “A”
DETAIL “A”
GAUGE PLANE
12
34
4.90 ± 0.152
(.193 ± .006)
8765
3.00 ± 0.102
(.118 ± .004)
(NOTE 3)
3.00 ± 0.102
(.118 ± .004)
(NOTE 4)
0.52
(.0205)
REF
5.23
(.206)
MIN
3.20 – 3.45
(.126 – .136)
0.889 ± 0.127
(.035 ± .005)
RECOMMENDED SOLDER PAD LAYOUT
0.42 ± 0.038
(.0165 ± .0015)
TYP
0.65
(.0256)
BSC
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
LTC6101/LTC6101HV
20
6101fh
1.50 – 1.75
(NOTE 4)
2.80 BSC
0.30 – 0.45 TYP
5 PLCS (NOTE 3)
DATUM ‘A’
0.09 – 0.20
(NOTE 3) S5 TSOT-23 0302 REV B
PIN ONE
2.90 BSC
(NOTE 4)
0.95 BSC
1.90 BSC
0.80 – 0.90
1.00 MAX
0.01 – 0.10
0.20 BSC
0.30 – 0.50 REF
NOTE:
1. DIMENSIONS ARE IN MILLIMETERS
2. DRAWING NOT TO SCALE
3. DIMENSIONS ARE INCLUSIVE OF PLATING
4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
5. MOLD FLASH SHALL NOT EXCEED 0.254mm
6. JEDEC PACKAGE REFERENCE IS MO-193
3.85 MAX
0.62
MAX
0.95
REF
RECOMMENDED SOLDER PAD LAYOUT
PER IPC CALCULATOR
1.4 MIN
2.62 REF
1.22 REF
S5 Package
5-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1635)
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
LTC6101/LTC6101HV
21
6101fh
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-
tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
REVISION HISTORY
REV DATE DESCRIPTION PAGE NUMBER
H 03/12 Updated Features
Updated Absolute Maximum Ratings and changed Order Information
Changed operating temperature range to specifi ed temperature range in Electrical Characteristics header
Changed TA value in curve G02 from 45°C to 25°C
1
2
4, 5
6
(Revision history begins at Rev H)
LTC6101/LTC6101HV
22
6101fh
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com
© LINEAR TECHNOLOGY CORPORATION 2005
LT 0312 REV H • PRINTED IN USA
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TYPICAL APPLICATION
L
O
A
D
CHARGER
–+
–+
+
–
V
OUT
= I
DISCHARGE
•
R
SENSE
( )
WHEN I
DISCHARGE
≥ 0DISCHARGING: R
OUT
R
IN D
V
OUT
= I
CHARGE
•
R
SENSE
( )
WHEN I
CHARGE
≥ 0CHARGING: R
OUT
R
IN C
6101 TA05
V
BATT
R
IN C
LTC6101
R
IN D
R
IN C
LTC6101
R
OUT
V
OUT
R
IN D
I
DISCHARGE
I
CHARGE
R
SENSE
V
+
V
–
OUT OUT
–IN+IN
V
+
V
–
–IN +IN
Bidirectional Current Sense Circuit with Combined Charge/Discharge Output