LT1028/LT1128 Ultralow Noise Precision High Speed Op Amps Features Description Voltage Noise 1.1nV/Hz Max at 1kHz 0.85nV/Hz Typ at 1kHz 1.0nV/Hz Typ at 10Hz 35nVP-P Typ, 0.1Hz to 10Hz n Voltage and Current Noise 100% Tested n Gain-Bandwidth Product LT1028: 50MHz Min LT1128: 13MHz Min n Slew Rate LT1028: 11V/s Min LT1128: 5V/s Min n Offset Voltage: 40V Max n Drift with Temperature: 0.8V/C Max n Voltage Gain: 7 Million Min n Available in 8-Lead SO Package The LT(R)1028(gain of -1 stable)/LT1128(gain of +1 stable) achieve a new standard of excellence in noise performance with 0.85nV/Hz 1kHz noise, 1.0nV/Hz 10Hz noise. This ultralow noise is combined with excellent high speed specifications (gain-bandwidth product is 75MHz for LT1028, 20MHz for LT1128), distortion-free output, and true precision parameters (0.1V/C drift, 10V offset voltage, 30 million voltage gain). Although the LT1028/ LT1128 input stage operates at nearly 1mA of collector current to achieve low voltage noise, input bias current is only 25nA. Applications L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. n n n n n n n n The LT1028/LT1128's voltage noise is less than the noise of a 50 resistor. Therefore, even in very low source impedance transducer or audio amplifier applications, the LT1028/LT1128's contribution to total system noise will be negligible. Low Noise Frequency Synthesizers High Quality Audio Infrared Detectors Accelerometer and Gyro Amplifiers 350 Bridge Signal Conditioning Magnetic Search Coil Amplifiers Hydrophone Amplifiers Typical Application Ultralow Noise 1M TIA Photodiode Amplifier 0.1F 4.32k 1M D PHOTO DIODE SFH213 VS- JFET NXP S BF862 4.99k VS- 0.5pF - VOUT = ~0.4V + IPD * 1M LT1028 + VS = 15V 1028 TA01 VOLTAGE NOISE DENSITY (nV/Hz) VS+ Voltage Noise vs Frequency 10 MAXIMUM VS = 15V TA = 25C 1/f CORNER = 14Hz TYPICAL 1 1/f CORNER = 3.5Hz 0.1 0.1 1 10 100 FREQUENCY (Hz) 1k 1028 TA02 1028fb 1 LT1028/LT1128 Absolute Maximum Ratings (Note 1) Supply Voltage -55C to 105C................................................... 22V 105C to 125C................................................... 16V Differential Input Current (Note 9)........................25mA Input Voltage...............................Equal to Supply Voltage Output Short-Circuit Duration........................... Indefinite Operating Temperature Range LT1028/LT1128AM, M (OBSOLETE).... -55C to 125C LT1028/LT1128AC, C (Note 11).............-40C to 85C Storage Temperature Range All Devices.......................................... -65C to 150C Lead Temperature (Soldering, 10 sec.)................... 300C Pin Configuration TOP VIEW VOS TRIM 8 VOS TRIM 1 7 V+ - -IN 2 6 OUT + +IN 3 4 V- (CASE) 5 OVERCOMP TOP VIEW VOS TRIM 1 -IN 2 - 7 +IN 3 + 6 V - 8 4 5 VOS TRIM V+ OUT OVERCOMP S8 PACKAGE 8-LEAD PLASTIC SOIC TJMAX = 135C, JA = 140C/W H PACKAGE 8-LEAD TO-5 METAL CAN TJMAX = 175C, JA = 140C/W, JC = 40C/W OBSOLETE PACKAGE TOP VIEW TOP VIEW VOS TRIM 1 -IN 2 - +IN 3 + V- 4 VOS TRIM 7 V+ 8 6 OUT 5 OVERCOMP N8 PACKAGE 8-LEAD PLASTIC DIP J8 PACKAGE 8-LEAD CERAMIC DIP TJMAX = 175C, JA = 140C/W, JC = 40C/W OBSOLETE PACKAGE NC 1 16 NC NC 2 15 NC 14 TRIM TRIM 3 -IN 4 - 13 V + +IN 5 + NC 7 12 OUT 11 OVERCOMP 10 NC NC 8 9 V- 6 NC SW PACKAGE 16-LEAD PLASTIC SOL TJMAX = 140C, JA = 130C/W NOTE: THIS DEVICE IS NOT RECOMMENDED FOR NEW DESIGNS 1028fb 2 LT1028/LT1128 Order Information LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE LT1028ACN8#PBF N/A LT1028ACN8 8-Lead PDIP 0C to 70C LT1028CN8#PBF N/A LT1028CN8 8-Lead PDIP 0C to 70C LT1128ACN8#PBF N/A LT1128ACN8 8-Lead PDIP 0C to 70C LT1128CN8#PBF N/A LT1128CN8 8-Lead PDIP 0C to 70C LT1028CS8#PBF LT1028CS8#TRPBF 1028 8-Lead Plastic Small Outline 0C to 70C LT1128CS8#PBF LT1128CS8#TRPBF 1128 8-Lead Plastic Small Outline 0C to 70C LT1028CSW#PBF LT1028CSW#TRPBF LT1028CSW 16-Lead Plastic SOIC (Wide) 0C to 70C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. Consult LTC Marketing for information on nonstandard lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ Electrical Characteristics VS = 15V, TA = 25C unless otherwise noted. LT1028AM/AC LT1128AM/AC SYMBOL PARAMETER CONDITIONS TYP MAX TYP MAX UNITS VOS VOS Time IOS IB en Input Offset Voltage Long Term Input Offset Voltage Stability Input Offset Current Input Bias Current Input Noise Voltage Input Noise Voltage Density (Note 2) (Note 3) 10 0.3 40 20 0.3 80 V V/Mo In Input Noise Current Density VCM = 0V VCM = 0V 0.1Hz to 10Hz (Note 4) fO = 10Hz (Note 5) fO = 1000Hz, 100% Tested fO = 10Hz (Notes 4 and 6) fO = 1000Hz, 100% Tested 12 25 35 1.00 0.85 4.7 1.0 50 90 75 1.7 1.1 10.0 1.6 18 30 35 1.0 0.9 4.7 1.0 100 180 90 1.9 1.2 12.0 1.8 nVP-P nV/Hz nV/Hz pA/Hz pA/Hz CMRR PSRR AVOL Input Resistance Common Mode Differential Mode Input Capacitance Input Voltage Range Common Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain VOUT Maximum Output Voltage Swing SR Slew Rate GBW Gain-Bandwidth Product ZO IS Open-Loop Output Impedance Supply Current 9.5 300 20 5 12.2 126 132 30.0 20.0 15.0 13.0 12.2 15.0 6.0 75 20 80 7.6 10.5 M k pF V dB dB V/V V/V V/V V V V/s V/s MHz MHz mA VCM = 11V VS = 4V to 18V RL 2k, VO = 12V RL 1k, VO = 10V RL 600, VO = 10V RL 2k RL 600 AVCL = -1 AVCL = -1 fO = 20kHz (Note 7) fO = 200kHz (Note 7) VO = 0, IO = 0 MIN LT1028M/AC LT1128M/AC LT1028 LT1128 LT1028 LT1128 11.0 114 117 7.0 5.0 3.0 12.3 11.0 11.0 5.0 50 13 300 20 5 12.2 126 133 30.0 20.0 15.0 13.0 12.2 15.0 6.0 75 20 80 7.4 MIN 11.0 110 110 5.0 3.5 2.0 12.0 10.5 11.0 4.5 50 11 nA nA 1028fb 3 LT1028/LT1128 Electrical Characteristics The l denotes the specifications which apply over the operating temperature range -55C TA 125C. VS = 15V, unless otherwise noted. LT1028AM LT1128AM SYMBOL PARAMETER CONDITIONS VOS VOS Temp IOS IB Input Offset Voltage Average Input Offset Drift (Note 2) (Note 8) l MIN VCM = 0V VCM = 0V l CMRR PSRR AVOL Input Offset Current Input Bias Current Input Voltage Range Common Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain VOUT IS Maximum Output Voltage Swing Supply Current l l l VCM = 10.3V VS = 4.5V to 16V RL 2k, VO = 10V RL 1k, VO = 10V RL 2k l l l l 10.3 106 110 3.0 2.0 10.3 l LT1028M LT1128M TYP MAX TYP MAX UNITS 30 0.2 120 0.8 MIN 45 0.25 180 1.0 V V/C 25 40 11.7 122 130 14.0 10.0 11.6 8.7 90 150 30 50 11.7 120 130 14.0 10.0 11.6 9.0 180 300 nA nA V dB dB V/V V/V V mA 10.3 100 104 2.0 1.5 10.3 11.5 13.0 The l denotes the specifications which apply over the operating temperature range 0C TA 70C. VS = 15V, unless otherwise noted. LT1028AC LT1128AC SYMBOL PARAMETER CONDITIONS MIN TYP LT1028C LT1128C MAX MIN TYP MAX UNITS VOS Input Offset Voltage (Note 2) l 15 80 30 125 V VOS Temp Average Input Offset Drift (Note 8) l 0.1 0.8 0.2 1.0 V/C IOS Input Offset Current VCM = 0V l 15 65 22 130 nA IB Input Bias Current VCM = 0V l 30 120 40 240 nA Input Voltage Range CMRR Common Mode Rejection Ratio VCM= 10.5V l 10.5 12.0 10.5 12.0 V l 110 124 106 124 dB PSRR Power Supply Rejection Ratio VS = 4.5V to 18V l 114 132 107 132 dB AVOL Large-Signal Voltage Gain RL 2k, VO = 10V RL 1k, VO = 10V l 5.0 4.0 25.0 18.0 3.0 2.5 25.0 18.0 V/V V/V VOUT Maximum Output Voltage Swing RL 2k RL 600 (Note 10) l 11.5 9.5 12.7 11.0 11.5 9.0 12.7 10.5 V V IS Supply Current l 8.0 10.5 8.2 11.5 mA 1028fb 4 LT1028/LT1128 Electrical Characteristics The l denotes the specifications which apply over the operating temperature range -40C TA 85C. VS = 15V, unless otherwise noted. (Note 11) LT1028AC LT1128AC SYMBOL PARAMETER VOS Input Offset Voltage VOS Temp Average Input Offset Drift IOS IB CONDITIONS MIN TYP l 20 (Note 8) l 0.2 Input Offset Current VCM = 0V l 20 Input Bias Current VCM = 0V l 35 LT1028C LT1128C MAX MIN TYP MAX UNITS 95 35 150 V 0.8 0.25 1.0 V/C 80 28 160 nA 140 45 280 nA 10.4 11.8 10.4 11.8 V CMRR Common Mode Rejection Ratio VCM = 10.5V l 108 123 102 123 dB PSRR Power Supply Rejection Ratio VS = 4.5V to 18V l 112 131 106 131 dB AVOL Large-Signal Voltage Gain RL 2k, VO = 10V RL 1k, VO = 10V l 4.0 3.0 20.0 14.0 2.5 2.0 20.0 14.0 V/V V/V VOUT Maximum Output Voltage Swing RL 2k l 11.0 12.5 11.0 12.5 IS Supply Current Input Voltage Range Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: Input Offset Voltage measurements are performed by automatic test equipment approximately 0.5 sec. after application of power. In addition, at TA = 25C, offset voltage is measured with the chip heated to approximately 55C to account for the chip temperature rise when the device is fully warmed up. Note 3: Long Term Input Offset Voltage Stability refers to the average trend line of Offset Voltage vs Time over extended periods after the first 30 days of operation. Excluding the initial hour of operation, changes in VOS during the first 30 days are typically 2.5V. Note 4: This parameter is tested on a sample basis only. Note 5: 10Hz noise voltage density is sample tested on every lot with the exception of the S8 and S16 packages. Devices 100% tested at 10Hz are available on request. l l 8.5 11.0 8.7 V 12.5 mA Note 6: Current noise is defined and measured with balanced source resistors. The resultant voltage noise (after subtracting the resistor noise on an RMS basis) is divided by the sum of the two source resistors to obtain current noise. Maximum 10Hz current noise can be inferred from 100% testing at 1kHz. Note 7: Gain-bandwidth product is not tested. It is guaranteed by design and by inference from the slew rate measurement. Note 8: This parameter is not 100% tested. Note 9: The inputs are protected by back-to-back diodes. Current-limiting resistors are not used in order to achieve low noise. If differential input voltage exceeds 1.8V, the input current should be limited to 25mA. Note 10: This parameter guaranteed by design, fully warmed up at TA = 70C. It includes chip temperature increase due to supply and load currents. Note 11: The LT1028/LT1128 are designed, characterized and expected to meet these extended temperature limits, but are not tested at -40C and 85C. Guaranteed I-grade parts are available. Consult factory. 1028fb 5 LT1028/LT1128 Typical Performance Characteristics 10Hz Voltage Noise Distribution 180 120 RMS VOLTAGE NOISE (V) 140 NUMBER OF UNITS 10 VS = 15V TA = 25C 500 UNITS MEASURED FROM 4 RUNS 158 148 160 Wideband Voltage Noise (0.1Hz to Frequency Indicated) Wideband Noise, DC to 20kHz 100 80 70 57 60 40 28 20 0 8 0.6 74 3 2 2 2 12 3 21 1 0.8 1.0 1.2 1.4 1.6 1.8 2.0 VOLTAGE NOISE DENSITY (nV/Hz) VERTICAL SCALE = 0.5V/DIV HORIZONTAL SCALE = 0.5ms/DIV 1 VS = 15V TA = 25C 1 0.1 1028 G02 0.01 100 2.2 1k 100k 10k BANDWIDTH (Hz) 1M 10M 1028 G03 1028 G01 Total Noise vs Matched Source Resistance Total Noise vs Unmatched Source Resistance + 10 AT 10Hz 1 AT 1kHz 2 RS NOISE ONLY VS = 15V TA = 25C 1 3 10 30 100 300 1k 3k MATCHED SOURCE RESISTANCE () 10k 10 AT 1kHz AT 10Hz 1 0.1 2 RS NOISE ONLY VS = 15V TA = 25C 1 VS = 15V TA = 25C 1/f CORNER = 250Hz 10 1028 G07 10 100 1k FREQUENCY (Hz) 0 20 1028 G06 RMS VOLTAGE DENSITY (nV/Hz) 60 40 TIME (SEC) 80 10k Voltage Noise vs Temperature 10nV 8 TYPICAL 1 2.0 VS = 15V TA = 25C 6 4 TIME (SEC) 1/f CORNER = 800Hz 0.01Hz to 1Hz Voltage Noise 10nV MAXIMUM 1028 G05 0.1Hz to 10Hz Voltage Noise 2 10 0.1 10 30 100 300 1k 3k 10k 3 UNMATCHED SOURCE RESISTANCE () 1028 G04 0 CURRENT NOISE DENSITY (pA/Hz) RS 100 RS - TOTAL NOISE DENSITY (nV/Hz) TOTAL NOISE DENSITY (nV/Hz) RS 0.1 Current Noise Spectrum 100 100 100 1028 G08 VS = 15V 1.6 1.2 0.8 AT 10Hz AT 1kHz O.4 0 -50 -25 50 25 0 75 TEMPERATURE (C) 100 125 1028 G09 1028fb 6 LT1028/LT1128 Typical Performance Characteristics Distribution of Input Offset Voltage 50 VS = 15V TA = 25C 800 UNITS TESTED FROM FOUR RUNS 16 40 14 UNITS (%) 10 12 10 8 6 20 10 0 -10 -20 4 -30 2 -40 0 -50 -40 -30 -20 -10 0 10 20 30 40 50 OFFSET VOLTAGE (V) -50 -50 -25 METAL CAN (H) PACKAGE 8 50 25 0 75 TEMPERATURE (C) 100 DUAL-IN-LINE PACKAGE PLASTIC (N) OR CERDIP (J) 0 1 2 3 4 TIME AFTER POWER ON (MINUTES) 50 30 BIAS CURRENT 10 OFFSET CURRENT 50 25 75 0 TEMPERATURE (C) SUPPLY CURRENT (mA) RMS VOLTAGE NOISE DENSITY (nV/Hz) AT 1kHz 0.75 100 125 5 10 15 SUPPLY VOLTAGE (V) 20 0 -20 -40 20 1028 G16 NEGATIVE INPUT CURRENT (OVERCANCELLED) DEVICE -80 -15 10 5 -10 0 -5 COMMON MODE INPUT VOLTAGE (V) 1028 G15 10 50 9 40 VS = 15V 7 6 VS = 5V 5 4 30 125 1028 G17 125C 0 -10 -40 100 VS = 15V 10 -30 50 25 0 75 TEMPERATURE (C) -50C 25C 20 -20 3 0 -50 -25 15 Output Short-Circuit Current vs Time 2 0 POSITIVE INPUT CURRENT (UNDERCANCELLED) DEVICE -60 1 0.5 60 40 Supply Current vs Temperature 8 5 RCM = 20V 300M VS = 15V TA = 25C 65nA 80 1028 G14 TA = 25C 1.0 4 100 20 Voltage Noise vs Supply Voltage AT 10Hz 3 2 TIME (MONTHS) Bias Current Over the Common Mode Range 40 0 -50 -25 5 1.25 1 0 1028 G12 VS = 15V VCM = 0V 1028 G13 1.5 125 SHORT-CIRCUIT CURRENT (mA) SINKING SOURCING 0 -4 -6 -10 INPUT BIAS CURRENT (nA) INPUT BIAS AND OFFSET CURRENTS (nA) CHANGE IN OFFSET VOLTAGE (V) 60 16 4 0 -2 Input Bias and Offset Currents Over Temperature VS = 15V TA = 25C 12 2 1028 G11 Warm-Up Drift 20 4 -8 1028 G10 24 VS = 15V 8 TA = 25C t = 0 AFTER 1 DAY PRE-WARM UP 6 VS = 15V 30 OFFSET VOLTAGE (V) 18 Long-Term Stability of Five Representative Units OFFSET VOLTAGE CHANGE (V) 20 Offset Voltage Drift with Temperature of Representative Units 125C 25C -50C -50 3 2 0 1 TIME FROM OUTPUT SHORT TO GROUND (MINUTES) 1028 G18 1028fb 7 LT1028/LT1128 Typical Performance Characteristics LT1028 Gain, Phase vs Frequency Voltage Gain vs Frequency 60 40 50 50 60 40 40 30 30 GAIN 20 20 10 20 0 0 -20 0.01 0.1 1 10 100 1k 10k 100k 1M 10M 100M FREQUENCY (Hz) 10 VS = 15V TA = 25C CL = 10pF -10 10k 100k 1M 10M FREQUENCY (Hz) LT1028 60 60 70 PHASE 10 1 FREQUENCY (Hz) 40 30 30 20 20 GAIN 10 VS = 15V TA = 25C CL = 10pF -10 10k 100 VOLTAGE GAIN (V/V) VOLTAGE GAIN (V/V) 100 RL = 2k RL = 600 20 1028 G25 100 1000 CAPACITIVE LOAD (pF) 100k - + 50 40 CL AV = -1, RS = 2k 30 AV = -10 RS = 200 10 -10 100M 1M 10M FREQUENCY (Hz) 2k RS 20 0 0 AV = -100, RS = 20 10 VS = 15V TA = 25C VO = 10mVP-P 100 1000 CAPACITIVE LOAD (pF) Maximum Undistorted Output vs Frequency 1 30 TA = 25C TA = 125C 10 ILMAX = 35mA AT -55C = 27mA AT 25C = 16mA AT 125C 0.1 1 LOAD RESISTANCE (k) 10000 1028 G24 VS = 15V TA = -55C 10000 30pF 60 Voltage Gain vs Load Resistance TA = 25C 5 10 15 SUPPLY VOLTAGE (V) 10 VS = 15V TA = 25C 1028 G23 Voltage Gain vs Supply Voltage 0 50 40 1028 G22 1 AV = -100 RS = 20 LT1128 Capacitance Load Handling 80 0 GAIN ERROR = CLOSED-LOOP GAIN OPEN-LOOP GAIN 10 AV = -10 RS = 200 1028 G21 70 10 100 0 CL AV = -1, RS = 2k 30 70 50 LT1128 VOLTAGE GAIN (dB) GAIN ERROR (%) TYPICAL PRECISION OP AMP 0.1 40 10 -10 100M - + 50 LT1128 Gain Phase vs Frequency 1 0.001 2k RS 1028 G20 Gain Error vs Frequency Closed-Loop Gain = 1000 0.01 30pF 20 0 1028 G19 0.1 OVERSHOOT (%) 80 LT1028 70 OVERSHOOT (%) LT1128 60 10 1028 G26 PEAK-TO-PEAK OUTPUT VOLTAGE (V) 100 80 PHASE MARGIN (DEG) 120 70 PHASE 60 VOLTAGE GAIN (dB) 140 VOLTAGE GAIN (dB) 70 VS = 15V TA = 25C RL = 2k PHASE MARGIN (DEG) 160 LT1028 Capacitance Load Handling VS = 15V TA = 25C RL = 2k 25 20 15 LT1128 LT1028 10 5 10k 100k 1M FREQUENCY (Hz) 10M 1028 G27 1028fb 8 LT1028/LT1128 Typical Performance Characteristics LT1028 Large-Signal Transient Response LT1028 Slew Rate, Gain-Bandwidth Product Over Temperature LT1028 Small-Signal Transient Response 50mV 5V/DIV 20mV/DIV -10V 17 SLEW RATE (V/s) 10V -50mV 1028 G28 1s/DIV AV = -1, RS = RF = 2k, CF = 15pF 90 VS = 15V 0.2s/DIV AV = -1, RS = RF = 2k, CF = 15pF, CL = 80pF 1028 G29 80 GBW 16 FALL 70 15 RISE 60 14 50 13 40 12 -50 -25 50 25 75 0 TEMPERATURE (C) 100 30 125 GAIN-BANDWIDTH PRODUCT (fO = 20kHz), (MHz) 18 1028 G30 LT1128 Small-Signal Transient Response 9 FALL 8 50mV 0V 0V -10V -50mV 7 RISE 6 SLEW RATE (V/s) 10V 30 GBW 5 4 20 3 2 1028 G31 2s/DIV AV = -1, RS = RF = 2k, CF = 30pF 0.2s/DIV 1028 G32 10 1 AV = -1, CL = 10pF 0 -50 -25 75 50 25 0 TEMPERATURE (C) 100 125 GAIN-BANDWIDTH PRODUCT (fO = 200kHz), (MHz) LT1128 Large-Signal Transient Response LT1128 Slew Rate, Gain-Bandwidth Product Over Temperature 1028 G33 LT1128 Slew Rate, Gain-Bandwidth Product vs Over-Compensation Capacitor Closed-Loop Output Impedance 100 10 10k LT1128 GBW 10 SLEW RATE 1 10 SLEW 10 100 1k 1 100 AV = 5 COC FROM PIN 5 TO PIN 6 VS = 15V TA = 25C LT1028 0.001 GBW GAIN AT 20kHz 0.1 0.01 100 SLEW RATE (V/s) LT1028 AV = 1000 1 1k LT1128 SLEW RATE (V/s) 10 100 IO = 1mA VS = 15V TA = 25C GAIN AT 200kHz OUTPUT IMPEDANCE () 100 LT1028 Slew Rate, Gain-Bandwidth Product vs Over-Compensation Capacitor 10k 1k FREQUENCY (Hz) 100k 1M 1028 G34 0.1 1 1 10 100 1000 10000 OVER-COMPENSATION CAPACITOR (pF) 1028 G35 0.1 1 10 10 100 1000 10000 OVER-COMPENSATION CAPACITOR (pF) 1028 G36 1028fb 9 LT1028/LT1128 Typical Performance Characteristics 140 -3 VS = 15V -4 4 3 VS = 5V TO 15V 2 1 V- 50 25 0 75 TEMPERATURE (C) -50 -25 100 120 100 LT1128 LT1028 80 60 40 20 0 125 10 100k 10k 1k FREQUENCY (Hz) 100 0.1 AV = -1000 RL = 2k AV = 1000 RL = 600 VO = 20VP-P VS = 15V TA = 25C 10 FREQUENCY (kHz) 1 100 TOTAL HARMONIC DISTORTION (%) TOTAL HARMONIC DISTORTION (%) AV = 1000 RL = 600 VO = 20VP-P f = 1kHz VS = 15V TA = 25C RL = 10k 0.01 INVERTING GAIN 0.001 0.0001 MEASURED EXTRAPOLATED 100 1k 10k CLOSED LOOP GAIN 10 0.1 VO = 20VP-P VS = 15V TA = 25C 10 FREQUENCY (kHz) 100 1028 G43 TOTAL HARMONIC DISTORTION (%) TOTAL HARMONIC DISTORTION (%) AV = 1000 RL = 600 AV = 1000 RL = 609 1.0 20 1 10 100 1k 10k 100k 1M 10M FREQUENCY (Hz) 1028 G39 100k 1.0 0.1 10k 100k FREQUENCY (Hz) 1M 1028 G42 1028 G41 AV = -1000 RL = 2k 0.001 40 LT1128 Total Harmonic Distortion vs Closed-Loop Gain 1.0 0.01 60 High Frequency Voltage Noise vs Frequency NON-INVERTING GAIN 1028 G40 0.1 POSITIVE SUPPLY 80 10 LT1128 Total Harmonic Distortion vs Frequency and Load Resistance AV = 1000 RL = 2k NEGATIVE SUPPLY 100 1028 G38 0.1 0.001 120 LT1028 Total Harmonic Distortion vs Closed-Loop Gain AV = 1000 RL = 2k VS = 15V TA = 25C 140 0 0.1 10M 1M 1028 G37 LT1028 Total Harmonic Distortion vs Frequency and Load Resistance 0.01 POWER SUPPLY REJECTION RATIO (dB) VS = 5V 160 VS = 15V TA = 25C NOISE VOLTAGE DENSITY (nV/Hz) COMMON MODE LIMIT (V) REFERRED TO POWER SUPPLY -1 -2 Power Supply Rejection Ratio vs Frequency Common Mode Rejection Ratio vs Frequency COMMON MODE REJECTION RATIO (dB) V+ Common Mode Limit Over Temperature 0.01 VO = 20VP-P f = 1kHz VS = 15V TA = 25C RL = 10k INVERTING GAIN 0.001 0.0001 NON-INVERTING GAIN MEASURED EXTRAPOLATED 10 100 1k 10k CLOSED LOOP GAIN 100k 1028 G44 1028fb 10 LT1028/LT1128 Applications Information - Noise Voltage Noise vs Current Noise The LT1028/LT1128's less than 1nV/Hz voltage noise is three times better than the lowest voltage noise heretofore available (on the LT1007/1037). A necessary condition for such low voltage noise is operating the input transistors at nearly 1mA of collector currents, because voltage noise is inversely proportional to the square root of the collector current. Current noise, however, is directly proportional to the square root of the collector current. Consequently, the LT1028/LT1128's current noise is significantly higher than on most monolithic op amps. Therefore, to realize truly low noise performance it is important to understand the interaction between voltage noise (en), current noise (In) and resistor noise (rn). Total Noise vs Source Resistance The total input referred noise of an op amp is given by: et = [en2 + rn2 + (InReq)2]1/2 where Req is the total equivalent source resistance at the two inputs, and rn = 4kTReq = 0.13Req in nV/Hz at 25C As a numerical example, consider the total noise at 1kHz of the gain 1000 amplifier shown in Figure 1. 100 The plot also shows that current noise is more dominant at low frequencies, such as 10Hz. This is because resistor noise is flat with frequency, while the 1/f corner of current noise is typically at 250Hz. At 10Hz when Req > 1k, the current noise term will exceed the resistor noise. When the source resistance is unmatched, the total noise versus unmatched source resistance plot should be consulted. Note that total noise is lower at source resistances below 1k because the resistor noise contribution is less. When RS > 1k total noise is not improved, however. This is because bias current cancellation is used to reduce input bias current. The cancellation circuitry injects two correlated current noise components into the two inputs. With matched source resistors the injected current noise creates a common-mode voltage noise and gets rejected by the amplifier. With source resistance in one input only, the cancellation noise is added to the amplifier's inherent noise. In summary, the LT1028/LT1128 are the optimum amplifiers for noise performance, provided that the source resistance is kept low. The following table depicts which op amp manufactured by Linear Technology should be used to minimize noise, as the source resistance is increased beyond the LT1028/LT1128's level of usefulness. 100k - 100 the largest term, as in the example above, and the LT1028/ LT1128's voltage noise becomes negligible. As Req is further increased, current noise becomes important. At 1kHz, when Req is in excess of 20k, the current noise component is larger than the resistor noise. The total noise versus matched source resistance plot illustrates the above calculations. LT1028 LT1128 + 1028 F01 Figure 1 Req = 100 + 100 || 100k 200 rn = 0.13200 = 1.84nVHz en = 0.85nVHz In = 1.0pA/Hz et = [0.852 + 1.842 + (1.0 x 0.2)2]1/2 = 2.04nV/Hz Output noise = 1000 et = 2.04V/Hz At very low source resistance (Req < 40) voltage noise dominates. As Req is increased resistor noise becomes Table 1. Best Op Amp for Lowest Total Noise vs Source Resistance BEST OP AMP SOURCE RESISTANCE () (Note 1) AT LOW FREQ (10Hz) WIDEBAND (1kHz) 0 to 400 LT1028/LT1128 LT1028/LT1128 400 to 4k LT1007/1037 LT1028/LT1128 4k to 40k LT1001 LT1007/LT1037 40k to 500k LT1012 LT1001 500k to 5M LT1012 or LT1055 LT1012 >5M LT1055 LT1055 Note 1: Source resistance is defined as matched or unmatched, e.g., RS = 1k means: 1k at each input, or 1k at one input and zero at the other. 1028fb 11 LT1028/LT1128 Applications Information - Noise Noise Testing - Voltage Noise The LT1028/LT1128's RMS voltage noise density can be accurately measured using the Quan Tech Noise Analyzer, Model 5173 or an equivalent noise tester. Care should be taken, however, to subtract the noise of the source resistor used. Prefabricated test cards for the Model 5173 set the device under test in a closed-loop gain of 31 with a 60 source resistor and a 1.8k feedback resistor. The noise of this resistor combination is 0.1358 = 1.0nV/Hz. An LT1028/LT1128 with 0.85nV/Hz noise will read (0.852 + 1.02)1/2 = 1.31nV/Hz. For better resolution, the resistors should be replaced with a 10 source and 300 feedback resistor. Even a 10 resistor will show an apparent noise which is 8% to 10% too high. The 0.1Hz to 10Hz peak-to-peak noise of the LT1028/ LT1128 is measured in the test circuit shown. The frequency response of this noise tester indicates that the 0.1Hz corner is defined by only one zero. The test time to measure 0.1Hz to 10Hz noise should not exceed 10 seconds, as this time limit acts as an additional zero to eliminate noise contributions from the frequency band below 0.1Hz. Measuring the typical 35nV peak-to-peak noise performance of the LT1028/LT1128 requires special test precautions: (a) The device should be warmed up for at least five minutes. As the op amp warms up, its offset voltage changes typically 10V due to its chip temperature increasing 30C to 40C from the moment the power supplies are turned on. In the 10 second measurement interval these temperature-induced effects can easily exceed tens of nanovolts. (b) For similar reasons, the device must be well shielded from air current to eliminate the possibility of thermoelectric effects in excess of a few nanovolts, which would invalidate the measurements. (c) Sudden motion in the vicinity of the device can also feedthrough to increase the observed noise. A noise-voltage density test is recommended when measuring noise on a large number of units. A 10Hz noise-voltage density measurement will correlate well with a 0.1Hz to 10Hz peak-to-peak noise reading since both results are determined by the white noise and the location of the 1/f corner frequency. 0.1F 100 90 100k 10 + 2k * 4.7F + LT1001 - 100k VOLTAGE GAIN = 50,000 24.3k * DEVICE UNDER TEST 4.3k 2.2F 22F SCOPE x1 RIN = 1M 110k 70 60 50 40 0.1F NOTE ALL CAPACITOR VALUES ARE FOR NONPOLARIZED CAPACITORS ONLY GAIN (dB) 80 - 1028 F02 30 0.01 0.1 1.0 10 FREQUENCY (Hz) 100 1028 F03 Figure 2. 0.1Hz to 10Hz Noise Test Circuit Figure 3. 0.1Hz to 10Hz Peak-to-Peak Noise Tester Frequency Response 1028fb 12 LT1028/LT1128 Applications Information - Noise Noise Testing - Current Noise Current noise density (In) is defined by the following formula, and can be measured in the circuit shown in Figure 4. e 2 - 31* 18.4nV/ Hz 2 no ln = 20k * 31 ( ) 1/2 1.8k 10k 60 10k 10Hz voltage noise density is sample tested on every lot. Devices 100% tested at 10Hz are available on request for an additional charge. 10Hz current noise is not tested on every lot but it can be inferred from 100% testing at 1kHz. A look at the current noise spectrum plot will substantiate this statement. The only way 10Hz current noise can exceed the guaranteed limits is if its 1/f corner is higher than 800Hz and/or its white noise is high. If that is the case then the 1kHz test will fail. - LT1028 LT1128 eno 10 + 1028 F04 If the Quan Tech Model 5173 is used, the noise reading is input-referred, therefore the result should not be divided by 31; the resistor noise should not be multiplied by 31. 100% Noise Testing The 1kHz voltage and current noise is 100% tested on the LT1028/LT1128 as part of automated testing; the approximate frequency response of the filters is shown. The limits on the automated testing are established by extensive correlation tests on units measured with the Quan Tech Model 5173. NOISE FILTER LOSS (dB) Figure 4 0 -10 -20 -30 CURRENT NOISE VOLTAGE NOISE -40 -50 100 1k 10k 100k FREQUENCY (Hz) 1028 F05 Figure 5. Automated Tester Noise Filter 1028fb 13 LT1028/LT1128 Applications Information General 10k* 15V The LT1028/LT1128 series devices may be inserted directly into OP-07, OP-27, OP-37, LT1007 and LT1037 sockets with or without removal of external nulling components. In addition, the LT1028/LT1128 may be fitted to 5534 sockets with the removal of external compensation components. 2 200* 10k* The input offset voltage of the LT1028/LT1128 and its drift with temperature, are permanently trimmed at wafer testing to a low level. However, if further adjustment of VOS is necessary, the use of a 1k nulling potentiometer will not degrade drift with temperature. Trimming to a value other than zero creates a drift of (VOS/300)V/C, e.g., if VOS is adjusted to 300V, the change in drift will be 1V/C. The adjustment range with a 1k pot is approximately 1.1mV. 1k INPUT 3 15V + VO 4 -15V 7 6 OUTPUT 4 -15V 1028 F07 Unity-Gain Buffer Applications (LT1128 Only) When RF 100 and the input is driven with a fast, largesignal pulse (>1V), the output waveform will look as shown in the pulsed operation diagram (Figure 8). RF - OUTPUT 8 LT1028 LT1128 + 6 Figure 7. Test Circuit for Offset Voltage and Offset Voltage Drift with Temperature 1 - 7 LT1028 LT1128 VO = 100VOS * RESISTORS MUST HAVE LOW THERMOELECTRIC POTENTIAL Offset Voltage Adjustment 2 3 - 6V/s + 1028 F08 Figure 8 1028 F06 Figure 6 Offset Voltage and Drift Thermocouple effects, caused by temperature gradients across dissimilar metals at the contacts to the input terminals, can exceed the inherent drift of the amplifier unless proper care is exercised. Air currents should be minimized, package leads should be short, the two input leads should be close together and maintained at the same temperature. The circuit shown in Figure 7 to measure offset voltage is also used as the burn-in configuration for the LT1028/ LT1128. During the fast feedthrough-like portion of the output, the input protection diodes effectively short the output to the input and a current, limited only by the output short-circuit protection, will be drawn by the signal generator. With RF 500, the output is capable of handling the current requirements (IL 20mA at 10V) and the amplifier stays in its active mode and a smooth transition will occur. As with all operational amplifiers when RF > 2k, a pole will be created with RF and the amplifier's input capacitance, creating additional phase shift and reducing the phase margin. A small capacitor (20pF to 50pF) in parallel with RF will eliminate this problem. 1028fb 14 LT1028/LT1128 Applications Information Frequency Response C1 The LT1028's Gain, Phase vs Frequency plot indicates that the device is stable in closed-loop gains greater than +2 or -1 because phase margin is about 50 at an open-loop gain of 6dB. In the voltage follower configuration phase margin seems inadequate. This is indeed true when the output is shorted to the inverting input and the noninverting input is driven from a 50 source impedance. However, when feedback is through a parallel R-C network (provided CF < 68pF), the LT1028 will be stable because of interaction between the input resistance and capacitance and the feedback network. Larger source resistance at the noninverting input has a similar effect. The following voltage follower configurations are stable: 33pF 2k - R1 RS1 RS2 - LT1028 + 1028 F10 Figure 10 If CF is only used to cut noise bandwidth, a similar effect can be achieved using the over-compensation terminal. The Gain, Phase plot also shows that phase margin is about 45 at gain of 10 (20dB). The following configuration has a high (70%) overshoot without the 10pF capacitor because of additional phase shift caused by the feedback resistor - input capacitance pole. The presence of the 10pF capacitor cancels this pole and reduces overshoot to 5%. - LT1028 500 + 50 10pF LT1028 + 10k 1.1k 50 - LT1028 + 1028 F09 Figure 9 Another configuration which requires unity-gain stability is shown below. When CF is large enough to effectively short the output to the input at 15MHz, oscillations can occur. The insertion of RS2 500 will prevent the LT1028 from oscillating. When RS1 500, the additional noise contribution due to the presence of RS2 will be minimal. When RS1 100, RS2 is not necessary, because RS1 represents a heavy load on the output through the CF short. When 100 < RS1 < 500, RS2 should match RS1. For example, RS1 = RS2 = 300 will be stable. The noise increase due to RS2 is 40%. 50 1028 F11 Figure 11 Over-Compensation The LT1028/LT1128 are equipped with a frequency overcompensation terminal (Pin 5). A capacitor connected between Pin 5 and the output will reduce noise bandwidth. Details are shown on the Slew Rate, Gain-Bandwidth Product vs Over-Compensation Capacitor plot. An additional benefit is increased capacitive load handling capability. 1028fb 15 LT1028/LT1128 Typical Applications Strain Gauge Signal Conditioner with Bridge Excitation 15V LT1021-5 3 5.0V + 2 - 7 330 6 LT1128 4 -15V REFERENCE OUTPUT 350 BRIDGE 3 301k* 10k ZERO TRIM 2 2 7 - + 6 LT1028 + 4 *RN60C FILM RESISTORS 6 LT1028 7 - 0V TO 10V OUTPUT 1F 30.1k* 5k GAIN TRIM 49.9* -15V 15V 3 15V 330 4 THE LT1028's NOISE CONTRIBUTION IS NEGLIGIBLE COMPARED TO THE BRIDGE NOISE. -15V 1028 TA03 Low Noise Voltage Regulator 28V LT317A 10 1k + LT1028 10 121 2.3k PROVIDES PRE-REG AND CURRENT LIMITING 28V LT1021-10 + 330 2N6387 - 1000pF 20V OUTPUT 2k 2k 1028 TA04 1028fb 16 LT1028/LT1128 Typical Applications Paralleling Amplifiers to Reduce Voltage Noise + A1 LT1028 1.5k - 7.5 470 4.7k + A2 LT1028 1.5k - - 7.5 LT1028 + An LT1028 OUTPUT + 470 1.5k - 7.5 470 1. ASSUME VOLTAGE NOISE OF LT1028 AND 7.5 SOURCE RESISTOR = 0.9nV/Hz. 2. GAIN WITH n LT1028s IN PARALLEL = n * 200. 3. OUTPUT NOISE = n * 200 * 0.9nV/Hz. OUTPUT NOISE 0.9 4. INPUT REFERRED NOISE = = nV/Hz. n * 200 n 5. NOISE CURRENT AT INPUT INCREASES n TIMES. 2V 6. IF n = 5, GAIN = 1000, BANDWIDTH = 1MHz, RMS NOISE, DC TO 1MHz = = 0.9V. 5 1028 TA05 1028fb 17 LT1028/LT1128 Typical Applications Phono Preamplifier 10 787 15V 2 3 + 0.33F 6 LT1028 47k 10k 7 - 100pF 0.1F OUTPUT 4 -15V ALL RESISTORS METAL FILM MAG PHONO INPUT 1028 TA06 Tape Head Amplifier 499 0.1F 31.6k 10 2 - LT1028 TAPE HEAD INPUT 3 6 OUTPUT + ALL RESISTORS METAL FILM 1028 TA07 1028fb 18 LT1028/LT1128 Typical Applications Low Noise, Wide Bandwidth Instrumentation Amplifier -INPUT + 300 LT1028 - 820 10k 68pF 50 10 820 - OUTPUT LT1028 300 LT1028 +INPUT - 68pF + + 10k GAIN = 1000, BANDWIDTH = 1MHz INPUT REFERRED NOISE = 1.5nV/Hz AT 1kHz WIDEBAND NOISE -DC to 1MHz = 3VRMS IF BW LIMITED TO DC TO 100kHz = 0.55VRMS 1028 TA08 Gyro Pick-Off Amplifier GYRO TYPICAL- NORTHROP CORP. GR-F5AH7-5B SINE DRIVE + * OUTPUT TO SYNC DEMODULATOR LT1028 - 1k 100 1028 TA09 1028fb 19 LT1028/LT1128 Typical Applications Super Low Distortion Variable Sine Wave Oscillator R1 C1 0.047 20 20 C2 0.047 2k 1VRMS OUTPUT 1.5kHz TO 15kHz 1 f= 2RC WHERE R1C1 = R2C2 4.7k 15V + 2k ( LT1028 R2 - 5.6k 2.4k ) LT1004-1.2V 10pF 22k 15F + 100k 560 LT1055 TRIM FOR LOWEST DISTORTION + 20k MOUNT 1N4148s IN CLOSE PROXIMITY - 2N4338 10k 10k <0.0018% DISTORTION AND NOISE. MEASUREMENT LIMITED BY RESOLUTION OF HP339A DISTORTION ANALYZER 1028 TA10 Chopper-Stabilized Amplifier 15V 1N758 3 7 + 2 LT1052 - 6 8 4 1 0.1 0.1 1N758 0.01 15V -15V 100k 130 68 1 INPUT 3 2 + 7 LT1028 - 30k 4 8 OUTPUT 10k -15V 10 1028 TA11 1028fb 20 LT1028/LT1128 Schematic Diagram NULL 8 R5 130 NULL 1 V+ 7 R6 130 Q4 R2 3k R1 3k 1.1mA R10 400 Q16 3 1 Q8 1 Q11 Q1 Q2 R11 100 Q9 Q24 4.5A OUTPUT 6 Q25 1.5A Q12 Q13 R12 240 Q14 1.5A INVERTING INPUT 2 Q22 C3 250pF Q10 4.5A 4.5A Q26 Q6 4.5A 3 R10 C2 500 Q18 Q5 Q7 500A R11 400 Q19 900A 3 NONINVERTING INPUT 400A C1 257pF Q17 900A 2.3mA C4 35pF Q27 0 1.8mA BIAS Q3 Q15 R7 80 V- 4 C2 = 50pF for LT1028 C2 = 275pF for LT1128 300A R8 480 Q23 Q21 600A Q20 1028 TA12 5 OVER-COMP 1028fb 21 LT1028/LT1128 Package Description Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. J8 Package 3-Lead CERDIP (Narrow .300 Inch, Hermetic) (Reference LTC DWG # 05-08-1110) CORNER LEADS OPTION (4 PLCS) .023 - .045 (0.584 - 1.143) HALF LEAD OPTION .045 - .068 (1.143 - 1.650) FULL LEAD OPTION .005 (0.127) MIN .405 (10.287) MAX 8 7 6 5 .025 (0.635) RAD TYP .220 - .310 (5.588 - 7.874) 1 .300 BSC (7.62 BSC) 2 3 4 .200 (5.080) MAX .015 - .060 (0.381 - 1.524) .008 - .018 (0.203 - 0.457) 0 - 15 NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE OR TIN PLATE LEADS .045 - .065 (1.143 - 1.651) .014 - .026 (0.360 - 0.660) .100 (2.54) BSC .125 3.175 MIN J8 0801 OBSOLETE PACKAGE 1028fb 22 LT1028/LT1128 Package Description Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. N Package 8-Lead PDIP (Narrow .300 Inch) (Reference LTC DWG # 05-08-1510 Rev I) .400* (10.160) MAX 8 7 6 5 1 2 3 4 .255 .015* (6.477 0.381) .300 - .325 (7.620 - 8.255) .008 - .015 (0.203 - 0.381) ( +.035 .325 -.015 8.255 +0.889 -0.381 ) .045 - .065 (1.143 - 1.651) .065 (1.651) TYP .100 (2.54) BSC .130 .005 (3.302 0.127) .120 (3.048) .020 MIN (0.508) MIN .018 .003 (0.457 0.076) N8 REV I 0711 NOTE: 1. DIMENSIONS ARE INCHES MILLIMETERS *THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .010 INCH (0.254mm) 1028fb 23 LT1028/LT1128 Package Description Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. S8 Package 8-Lead Plastic Small Outline (Narrow .150 Inch) (Reference LTC DWG # 05-08-1610 Rev G) .050 BSC .189 - .197 (4.801 - 5.004) NOTE 3 .045 .005 8 .245 MIN .160 .005 .010 - .020 x 45 (0.254 - 0.508) NOTE: 1. DIMENSIONS IN 5 .150 - .157 (3.810 - 3.988) NOTE 3 1 RECOMMENDED SOLDER PAD LAYOUT .053 - .069 (1.346 - 1.752) 0- 8 TYP .016 - .050 (0.406 - 1.270) 6 .228 - .244 (5.791 - 6.197) .030 .005 TYP .008 - .010 (0.203 - 0.254) 7 .014 - .019 (0.355 - 0.483) TYP INCHES (MILLIMETERS) 2. DRAWING NOT TO SCALE 3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm) 4. PIN 1 CAN BE BEVEL EDGE OR A DIMPLE 2 3 4 .004 - .010 (0.101 - 0.254) .050 (1.270) BSC SO8 REV G 0212 1028fb 24 LT1028/LT1128 Package Description Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. S Package 16-Lead Plastic Small Outline (Narrow .150 Inch) (Reference LTC DWG # 05-08-1610 Rev G) .386 - .394 (9.804 - 10.008) NOTE 3 .045 .005 .050 BSC 16 N 14 13 12 11 10 9 N .245 MIN .160 .005 .150 - .157 (3.810 - 3.988) NOTE 3 .228 - .244 (5.791 - 6.197) 1 .030 .005 TYP 15 2 3 N/2 N/2 RECOMMENDED SOLDER PAD LAYOUT .010 - .020 x 45 (0.254 - 0.508) .008 - .010 (0.203 - 0.254) 1 2 3 4 5 .053 - .069 (1.346 - 1.752) NOTE: 1. DIMENSIONS IN .014 - .019 (0.355 - 0.483) TYP 7 8 .004 - .010 (0.101 - 0.254) 0 - 8 TYP .016 - .050 (0.406 - 1.270) 6 .050 (1.270) BSC S16 REV G 0212 INCHES (MILLIMETERS) 2. DRAWING NOT TO SCALE 3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm) 4. PIN 1 CAN BE BEVEL EDGE OR A DIMPLE 1028fb 25 LT1028/LT1128 Package Description Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. H Package 8-Lead TO-5 Metal Can (.230 Inch PCD) (Reference LTC DWG # 05-08-1321) .040 (1.016) MAX .335 - .370 (8.509 - 9.398) DIA .305 - .335 (7.747 - 8.509) .050 (1.270) MAX SEATING PLANE .165 - .185 (4.191 - 4.699) GAUGE PLANE .010 - .045* (0.254 - 1.143) REFERENCE PLANE .500 - .750 (12.700 - 19.050) .016 - .021** (0.406 - 0.533) .027 - .045 (0.686 - 1.143) 45 .028 - .034 (0.711 - 0.864) PIN 1 .230 (5.842) TYP .110 - .160 (2.794 - 4.064) INSULATING STANDOFF *LEAD DIAMETER IS UNCONTROLLED BETWEEN THE REFERENCE PLANE AND THE SEATING PLANE .016 - .024 **FOR SOLDER DIP LEAD FINISH, LEAD DIAMETER IS (0.406 - 0.610) H8 (TO-5) 0.230 PCD 0204 OBSOLETE PACKAGE 1028fb 26 LT1028/LT1128 Revision History (Revision history begins at Rev B) REV DATE DESCRIPTION B 10/12 Replaced the Typical Application. PAGE NUMBER 1 1028fb Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 27 LT1028/LT1128 Typical Application Low Noise Infrared Detector 5V 10 + 1k 100F 33 + SYNCHRONOUS DEMODULATOR 100F 10k* OPTICAL CHOPPER WHEEL 5V 5V 1000F 3 + IR RADIATION 10k* 267 39 2 PHOTOELECTRIC PICK-OFF 2 7 + LT1028 - 1/4 LTC1043 6 13 8 4 12 10k -5V INFRA RED ASSOCIATES, INC. HgCdTe IR DETECTOR 13 AT 77K 3 7 + LM301A - 1 4 14 16 -5V 30pF 5V 6 8 2 1M 3 7 + LT1012 - 4 10 6 8 DC OUT 1 -5V 1028 TA13 Related Parts PART NUMBER DESCRIPTION COMMENTS LT1806/LT1807 325MHz, 3.5nV/Hz Single and Dual Op Amps Slew Rate = 140V/s, Low Distortion at 5MHz: -80dBc 1028fb 28 Linear Technology Corporation LT 1012 REV B * PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 FAX: (408) 434-0507 www.linear.com LINEAR TECHNOLOGY CORPORATION 1992