Low Cost, High Speed, Rail-to-Rail Amplifiers AD8051/AD8052/AD8054 Active filters Analog-to-digital drivers Clock buffer Consumer video Professional cameras CCD imaging systems CD/DVD ROMs 8 NC -IN 2 7 +VS +IN 3 6 VOUT -VS 4 5 NC NC = NO CONNECT VOUT 1 -VS 2 -IN1 2 - + +IN1 3 - + -VS 4 8 +VS 7 OUT 6 -IN2 5 +IN2 4 -IN Figure 2. SOT-23-5 (RJ) Figure 3. SOIC (R-8) and MSOP (RM-8) OUT D OUT A 1 14 -IN A 2 13 -IN D +IN A 3 12 +IN D V+ 4 01062-003 OUT1 1 5 +VS + - +IN 3 Figure 1. SOIC-8 (R) AD8052 AD8051 01062-002 AD8051 AD8054 11 V- +IN B 5 10 +IN C -IN B 6 9 -IN C OUT B 7 8 OUT C 01062-004 NC 1 Figure 4. SOIC (R-14) and TSSOP (RU-14) 5.0 4.5 4.0 3.5 VS = 5V G = -1 RF = 2k RL = 2k 3.0 2.5 2.0 1.5 1.0 0.5 0 0.1 1 FREQUENCY (MHz) 10 50 01062-005 APPLICATIONS PIN CONNECTIONS (TOP VIEWS) PEAK-TO-PEAK OUTPUT VOLTAGE SWING (THD 0.5%) (V) High speed and fast settling on 5 V 110 MHz, -3 dB bandwidth (G = +1) (AD8051/AD8052) 150 MHz, -3 dB bandwidth (G = +1) (AD8054) 145 V/s slew rate 50 ns settling time to 0.1% Single-supply operation Output swings to within 25 mV of either rail Input voltage range: -0.2 V to +4 V; VS = 5 V Video specifications (G = +2) 0.1 dB gain flatness: 20 MHz; RL = 150 Differential gain/phase: 0.03%/0.03 Low distortion -80 dBc total harmonic @ 1 MHz, RL = 100 Outstanding load drive capability Drives 45 mA, 0.5 V from supply rails (AD8051/AD8052) Drives 50 pF capacitive load (G = +1) (AD8051/AD8052) Low power: 2.75 mA/amplifier (AD8054) Low power: 4.4 mA/amplifier (AD8051/AD8052) 01062-001 FEATURES Figure 5. Low Distortion Rail-to-Rail Output Swing GENERAL DESCRIPTION The AD8051 (single), AD8052 (dual), and AD8054 (quad) are low cost, high speed, voltage feedback amplifiers. The amplifiers operate on +3 V, +5 V, or 5 V supplies at low supply current. They have true single-supply capability with an input voltage range extending 200 mV below the negative rail and within 1 V of the positive rail. Despite their low cost, the AD8051/AD8052/AD8054 provide excellent overall performance and versatility. The output voltage swings to within 25 mV of each rail, providing maximum output dynamic range with excellent overdrive recovery. The AD8051/AD8052/AD8054 are well suited for video electronics, cameras, video switchers, or any high speed portable equipment. Low distortion and fast settling make them ideal for active filter applications. The AD8051/AD8052 in the 8-lead SOIC, the AD8052 in the MSOP, the AD8054 in the 14-lead SOIC, and the 14-lead TSSOP packages are available in the extended temperature range of -40C to +125C. Rev. J Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 (c)2009 Analog Devices, Inc. All rights reserved. AD8051/AD8052/AD8054 TABLE OF CONTENTS Features .............................................................................................. 1 Circuit Description .................................................................... 16 Applications ....................................................................................... 1 Application Information ................................................................ 17 Pin Connections (Top Views) ......................................................... 1 Overdrive Recovery ................................................................... 17 General Description ......................................................................... 1 Driving Capacitive Loads .......................................................... 17 Revision History ............................................................................... 2 Layout Considerations ............................................................... 18 Specifications..................................................................................... 3 Active Filters ............................................................................... 18 Absolute Maximum Ratings............................................................ 9 Analog-to-Digital and Digital-to-Analog Applications ........ 19 Thermal Resistance ...................................................................... 9 Sync Stripper ............................................................................... 20 Maximum Power Dissipation ..................................................... 9 Single-Supply Composite Video Line Driver ......................... 20 ESD Caution .................................................................................. 9 Outline Dimensions ....................................................................... 21 Typical Performance Characteristics ........................................... 10 Ordering Guide .......................................................................... 23 Theory of Operation ...................................................................... 16 REVISION HISTORY 7/09--Rev. I to Rev. J Changes to Figure 22 ...................................................................... 12 12/08--Rev. H to Rev. I Change to Settling Time to 0.1% Parameter, Table 1 ................... 3 Updated Outline Dimensions ....................................................... 20 12/07--Rev. G to Rev. H Changes to Applications .................................................................. 1 Updated Outline Dimensions ....................................................... 21 Changes to Ordering Guide .......................................................... 23 5/06--Rev. F to Rev. G Updated Format .................................................................. Universal Changes to Features, Applications, and General Description .....1 Changes to Figure 15 ...................................................................... 12 Changes to the Ordering Guide.................................................... 22 2/03--Rev. C to Rev. D Changes to General Description ..................................................... 1 Changes to Specifications ................................................................. 3 Changes to Absolute Maximum Ratings ........................................ 6 1/03--Rev. B to Rev. C Changes to General Description ..................................................... 1 Changes to Pin Connections............................................................ 1 Changes to Specifications ................................................................. 2 Changes to Absolute Maximum Ratings ........................................ 9 Changes to Figure 2 ........................................................................... 9 Changes to Ordering Guide ............................................................. 9 Updated Outline Dimensions ........................................................20 9/04--Rev. E to Rev. F Changes to Ordering Guide .............................................................7 Changes to Figure 15 ...................................................................... 15 3/04--Rev. D to Rev. E Changes to General Description .....................................................2 Changes to Specifications .................................................................3 Changes to Ordering Guide .............................................................6 Rev. J | Page 2 of 24 AD8051/AD8052/AD8054 SPECIFICATIONS @ TA = 25C, VS = 5 V, RL = 2 k to 2.5 V, unless otherwise noted. Table 1. Parameter DYNAMIC PERFORMANCE -3 dB Small Signal Bandwidth Bandwidth for 0.1 dB Flatness Slew Rate Full Power Response Settling Time to 0.1% NOISE/DISTORTION PERFORMANCE Total Harmonic Distortion1 Input Voltage Noise Input Current Noise Differential Gain Error (NTSC) Differential Phase Error (NTSC) Crosstalk DC PERFORMANCE Input Offset Voltage Conditions G = +1, VOUT = 0.2 V p-p G = -1, +2, VOUT = 0.2 V p-p G = +2, VOUT = 0.2 V p-p, RL = 150 to 2.5 V RF = 806 (AD8051A/ AD8052A) RF = 200 (AD8054A) G = -1, VOUT = 2 V step G = +1, VOUT = 2 V p-p G = -1, VOUT = 2 V step AD8051A/AD8052A Min Typ Max Min 70 80 110 50 100 fC = 5 MHz, VOUT = 2 V p-p, G = +2 f = 10 kHz f = 10 kHz G = +2, RL = 150 to 2.5 V RL = 1 k to 2.5 V G = +2, RL = 150 to 2.5 V RL = 1 k to 2.5 V f = 5 MHz, G = +2 Offset Drift Input Bias Current MHz V/s MHz ns -67 -68 dB 16 850 0.09 0.03 0.19 0.03 -60 16 850 0.07 0.02 0.26 0.05 -60 nV/Hz fA/Hz % % Degrees Degrees dB TMIN - TMAX 76 INPUT CHARACTERISTICS Input Resistance Input Capacitance Input Common-Mode Voltage Range Common-Mode Rejection Ratio VCM = 0 V to 3.5 V MHz MHz 12 170 45 40 10 1.4 86 72 Rev. J | Page 3 of 24 Unit MHz 145 35 50 1.7 RL = 2 k to 2.5 V TMIN - TMAX RL = 150 to 2.5 V TMIN - TMAX 150 60 20 TMIN - TMAX Input Offset Current Open-Loop Gain AD8054A Typ Max 0.1 98 96 82 78 290 1.4 -0.2 to +4 88 140 10 25 1.7 15 2 2.5 3.25 0.75 82 74 70 0.2 98 96 82 78 300 1.5 -0.2 to +4 86 12 30 4.5 4.5 1.2 mV mV V/C A A A dB dB dB dB k pF V dB AD8051/AD8052/AD8054 Parameter OUTPUT CHARACTERISTICS Output Voltage Swing AD8051A/AD8052A Min Typ Max Conditions RL = 10 k to 2.5 V RL = 2 k to 2.5 V 0.1 to 4.9 0.3 to 4.625 RL = 150 to 2.5 V Output Current Short-Circuit Current Capacitive Load Drive POWER SUPPLY Operating Range Quiescent Current/Amplifier Power Supply Rejection Ratio OPERATING TEMPERATURE RANGE 1 VOUT = 0.5 V to 4.5 V TMIN - TMAX Sourcing Sinking G = +1 (AD8051/AD8052) G = +2 (AD8054) 0.015 to 4.985 0.025 to 4.975 0.2 to 4.8 45 45 80 130 50 0.125 to 4.875 0.55 to 4.4 AD8054A Typ Max 70 -40 -40 Refer to Figure 19. Rev. J | Page 4 of 24 4.4 80 12 5 3 68 +85 +125 -40 2.75 80 Unit V 0.03 to 4.975 0.05 to 4.95 0.25 to 4.65 30 30 45 85 V V mA mA mA mA pF pF 40 3 VS = 1 V RJ-5 RM-8, R-8, RU-14, R-14 Min 12 3.275 +125 V mA dB C C AD8051/AD8052/AD8054 @ TA = 25C, VS = 3 V, RL = 2 k to 1.5 V, unless otherwise noted. Table 2. Parameter DYNAMIC PERFORMANCE -3 dB Small Signal Bandwidth Bandwidth for 0.1 dB Flatness Slew Rate Full Power Response Settling Time to 0.1% NOISE/DISTORTION PERFORMANCE Total Harmonic Distortion1 Input Voltage Noise Input Current Noise Differential Gain Error (NTSC) Differential Phase Error (NTSC) Crosstalk DC PERFORMANCE Input Offset Voltage Conditions G = +1, VOUT = 0.2 V p-p G = -1, +2, VOUT = 0.2 V p-p G = +2, VOUT = 0.2 V p-p, RL = 150 to 2.5 V RF = 402 (AD8051A/ AD8052A) RF = 200 (AD8054A) G = -1, VOUT = 2 V step G = +1, VOUT = 1 V p-p G = -1, VOUT = 2 V step AD8051A/AD8052A Min Typ Max Min 70 80 110 50 90 fC = 5 MHz, VOUT = 2 V p-p, G = -1, RL = 100 to 1.5 V f = 10 kHz f = 10 kHz G = +2, VCM = 1 V RL = 150 to 1.5 V RL = 1 k to 1.5 V G = +2, VCM = 1 V RL = 150 to 1.5 V RL = 1 k to 1.5 V f = 5 MHz, G = +2 Offset Drift Input Bias Current MHz V/s MHz ns -47 -48 dB 16 600 16 600 nV/Hz fA/Hz 0.11 0.09 0.13 0.09 % % 0.24 0.10 -60 0.3 0.1 -60 Degrees Degrees dB 10 1.3 80 74 INPUT CHARACTERISTICS Input Resistance Input Capacitance Input Common-Mode Voltage Range VCM = 0 V to 1.5 V MHz MHz 10 150 85 55 TMIN - TMAX Common-Mode Rejection Ratio 135 65 72 Rev. J | Page 5 of 24 Unit MHz 135 65 55 1.6 RL = 2 k TMIN - TMAX RL = 150 TMIN - TMAX Max 17 TMIN - TMAX Input Offset Current Open-Loop Gain AD8054A Typ 0.15 96 94 82 76 290 1.4 -0.2 to +2 88 110 10 25 1.6 15 2 2.6 3.25 0.8 80 72 70 0.2 96 94 80 76 300 1.5 -0.2 to +2 86 12 30 4.5 4.5 1.2 mV mV V/C A A A dB dB dB dB k pF V dB AD8051/AD8052/AD8054 Parameter OUTPUT CHARACTERISTICS Output Voltage Swing AD8051A/AD8052A Min Typ Max Conditions RL = 10 k to 1.5 V RL = 2 k to 1.5 V 0.0.75 to 2.9 0.2 to 2.75 RL = 150 to 1.5 V Output Current Short-Circuit Current Capacitive Load Drive POWER SUPPLY Operating Range Quiescent Current/Amplifier Power Supply Rejection Ratio OPERATING TEMPERATURE RANGE 1 VOUT = 0.5 V to 2.5 V TMIN - TMAX Sourcing Sinking G = +1 (AD8051/AD8052) G = +2 (AD8054) 0.01 to 2.99 0.02 to 2.98 0.125 to 2.875 45 45 60 90 45 0.1 to 2.9 0.35 to 2.55 AD8054A Typ Max 68 -40 -40 Refer to Figure 19. Rev. J | Page 6 of 24 4.2 80 12 4.8 3 68 +85 +125 -40 2.625 80 Unit V 0.025 to 2.98 0.35 to 2.965 0.15 to 2.75 25 25 30 50 V V mA mA mA mA pF pF 35 3 VS = 0.5 V RJ-5 RM-8, R-8, RU-14, R-14 Min 12 3.125 +125 V mA dB C C AD8051/AD8052/AD8054 @ TA = 25C, VS = 5 V, RL = 2 k to ground, unless otherwise noted. Table 3. Parameter DYNAMIC PERFORMANCE -3 dB Small Signal Bandwidth Bandwidth for 0.1 dB Flatness Slew Rate Full Power Response Settling Time to 0.1% NOISE/DISTORTION PERFORMANCE Total Harmonic Distortion Input Voltage Noise Input Current Noise Differential Gain Error (NTSC) Differential Phase Error (NTSC) Crosstalk DC PERFORMANCE Input Offset Voltage Conditions G = +1, VOUT = 0.2 V p-p G = -1, +2, VOUT = 0.2 V p-p G = +2, VOUT = 0.2 V p-p, RL = 150 , RF = 1.1 k (AD8051A/ AD8052A) RF = 200 (AD8054A) G = -1, VOUT = 2 V step G = +1, VOUT = 2 V p-p G = -1, VOUT = 2 V step AD8051A/AD8052A Min Typ Max Min 70 85 110 50 105 fC = 5 MHz, VOUT = 2 V p-p, G = +2 f = 10 kHz f = 10 kHz G = +2, RL = 150 RL = 1 k G = +2, RL = 150 RL = 1 k f = 5 MHz, G = +2 Offset Drift Input Bias Current MHz V/s MHz MHz -71 -72 dB 16 900 0.02 0.02 0.11 0.02 -60 16 900 0.06 0.02 0.15 0.03 -60 nV/Hz fA/Hz % % Degrees Degrees dB 10 1.4 88 78 INPUT CHARACTERISTICS Input Resistance Input Capacitance Input Common-Mode Voltage Range VCM = -5 V to +3.5 V 72 RL = 10 k RL = 2 k -4.85 to +4.85 -4.45 to +4.3 RL = 150 Output Current Short-Circuit Current Capacitive Load Drive MHz MHz 15 190 50 40 TMIN - TMAX Common-Mode Rejection Ratio OUTPUT CHARACTERISTICS Output Voltage Swing 160 65 VOUT = -4.5 V to +4.5 V TMIN - TMAX Sourcing Sinking G = +1 (AD8051/AD8052) G = +2 (AD8054) Rev. J | Page 7 of 24 Unit MHz 170 40 50 1.8 RL = 2 k TMIN - TMAX RL = 150 TMIN - TMAX Max 20 TMIN - TMAX Input Offset Current Open-Loop Gain AD8054A Typ 0.1 96 96 82 80 290 1.4 -5.2 to +4 88 -4.98 to +4.98 -4.97 to +4.97 -4.6 to +4.6 45 45 100 160 50 150 11 27 1.8 15 2 2.6 3.5 0.75 84 76 70 -4.8 to +4.8 -4.0 to +3.8 0.2 96 96 82 80 13 32 4.5 4.5 1.2 mV mV V/C A A A dB dB dB dB 300 1.5 -5.2 to +4 86 k pF V -4.97 to +4.97 -4.9 to +4.9 -4.5 to +4.5 30 30 60 100 V 40 dB V V mA mA mA mA pF pF AD8051/AD8052/AD8054 Parameter POWER SUPPLY Operating Range Quiescent Current/Amplifier Power Supply Rejection Ratio OPERATING TEMPERATURE RANGE Conditions VS = 1 RJ-5 RM-8, R-8, RU-14, R-14 AD8051A/AD8052A Min Typ Max Min 3 3 68 -40 -40 Rev. J | Page 8 of 24 4.8 80 12 5.5 68 +85 +125 -40 AD8054A Typ 2.875 80 Max Unit 12 3.4 V mA dB C C +125 AD8051/AD8052/AD8054 ABSOLUTE MAXIMUM RATINGS MAXIMUM POWER DISSIPATION Table 4. Ratings 12.6 V MSOP Package TSSOP Package Input Voltage (Common Mode) Differential Input Voltage Output Short-Circuit Duration Storage Temperature Range (R) Operating Temperature Range (A Grade) Lead Temperature (Soldering 10 sec) 1 Observe power derating curves Observe power derating curves Observe power derating curves Observe power derating curves VS 2.5 V Observe power derating curves -65C to +150C -40C to +125C 300C While the AD8051/AD8052/AD8054 are internally shortcircuit protected, this cannot be sufficient to guarantee that the maximum junction temperature (150C) is not exceeded under all conditions. To ensure proper operation, it is necessary to observe the maximum power derating curves. 2.5 See Table 5. Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. TSSOP-14 SOIC-8 1.5 1.0 MSOP-8 0.5 0 -55 THERMAL RESISTANCE SOT-23-5 -35 -15 5 15 35 55 75 95 AMBIENT TEMPERATURE (C) Specification is for device in free air. Figure 6. Maximum Power Dissipation vs. Temperature for AD8051/AD8052/AD8054 Table 5. Thermal Resistance Package Type 8-Lead SOIC 5-Lead SOT-23 8-Lead MSOP 14-Lead SOIC 14-Lead TSSOP SOIC-14 2.0 JA 125 180 150 90 120 Unit C/W C/W C/W C/W C/W ESD CAUTION Rev. J | Page 9 of 24 115 01062-006 SOT-23 Package The maximum power that can be safely dissipated by the AD8051/AD8052/AD8054 is limited by the associated rise in junction temperature. The maximum safe junction temperature for plastic encapsulated devices is determined by the glass transition temperature of the plastic, approximately 150C. Temporarily exceeding this limit can cause a shift in parametric performance due to a change in the stresses exerted on the die by the package. Exceeding a junction temperature of 175C for an extended period can result in device failure. MAXIMUM POWER DISSIPATION (W) Parameter Supply Voltage Internal Power Dissipation1 SOIC Packages AD8051/AD8052/AD8054 TYPICAL PERFORMANCE CHARACTERISTICS 5 2 G = +5 RF = 2k -1 G = +1 RF = 0 G = +10 RF = 2k -3 -5 -6 -7 0.1 VS = 5V GAIN AS SHOWN RF AS SHOWN RL = 2k VOUT = 0.2V p-p 1 10 FREQUENCY (MHz) 100 500 -4 G = +5 RF = 2k VS = +3V 4 5V GAIN (dB) 1 0 -5 -2 -6 -3 10 FREQUENCY (MHz) 100 500 +3V +5V -4 100k 01062-008 1 5V Figure 8. AD8051/AD8052 Gain vs. Frequency vs. Supply 4 2 3 VS = 5V RL = 2k TO 2.5V CL = 5pF G = +1 VOUT = 0.2V p-p -40C 2 0 GAIN (dB) +25C -2 -3 500M +85C +25C -40C 0 -1 -3 -4 100 500 -5 01062-009 10 FREQUENCY (MHz) 100M -2 VS = 5V G = +1 RL = 2k VOUT = 0.2V p-p TEMPERATURE AS SHOWN 1 10M FREQUENCY (Hz) 1 +85C -1 1M Figure 11. AD8054 Gain vs. Frequency vs. Supply 3 1 GAIN (dB) +5V 2 -1 -6 500M +3V 3 VS = 5V -4 -7 0.1 100M G = +1 RL = 2k CL = 5pF VOUT = 0.2V p-p 5 VS = +5V -3 -5 10M FREQUENCY (Hz) Figure 10. AD8054 Normalized Gain vs. Frequency; VS = 5 V -2 -4 1M 6 VS AS SHOWN G = +1 RL = 2k VOUT = 0.2V p-p -1 -7 0.1 G = +10 RF = 2k -3 -7 100k 0 GAIN (dB) -2 -6 3 1 0 -1 -5 Figure 7. AD8051/AD8052 Normalized Gain vs. Frequency; VS = 5 V 2 1 01062-011 -4 2 G = +1 RF = 0 G = +2 RF = 2k 1 10 FREQUENCY (MHz) 100 500 Figure 12. AD8054 Gain vs. Frequency vs. Temperature Figure 9. AD8051/AD8052 Gain vs. Frequency vs. Temperature Rev. J | Page 10 of 24 01062-012 -2 NORMALIZED GAIN (dB) 0 3 01062-007 NORMALIZED GAIN (dB) 1 VS = 5V GAIN AS SHOWN RF AS SHOWN RL = 5k VOUT = 0.2V p-p 4 G = +2 RF = 2k 01062-010 3 6.3 6.2 6.2 6.1 6.1 GAIN FLATNESS (dB) 6.3 5.9 5.8 5.7 5.3 0.1 5.7 5.5 5.4 100 1 10 FREQUENCY (MHz) 5.3 VS = +5V VOUT = 2V p-p 8 7 6 6 5 5 GAIN (dB) 7 4 3 VS AS SHOWN G = +2 RF = 2k RL = 2k VOUT AS SHOWN -1 0.1 1 VS = 5V VOUT = 4V p-p 0 10 FREQUENCY (MHz) 100 500 VS AS SHOWN G = +2 RF = 2k RL = 2k VOUT AS SHOWN -1 0.1 1 10 FREQUENCY (MHz) 100 500 Figure 17. AD8054 Large Signal Frequency Response; G = +2 80 80 VS = 5V RL = 2k 70 VS = 5V RL = 2k CL = 5pF 70 60 GAIN 0 30 20 PHASE 50 PHASE MARGIN -45 10 -90 0 -135 -10 -180 0.1 1 10 FREQUENCY (MHz) 100 500 OPEN-LOOP GAIN (dB) 40 50 40 GAIN 180 30 20 PHASE 10 45 PHASE MARGIN 0 -20 30k Figure 15. AD8051/AD8052 Open-Loop Gain and Phase vs. Frequency 135 90 45 0 -10 01062-015 50 PHASE MARGIN (Degrees) 60 OPEN-LOOP GAIN (dB) VS = 5V VOUT = 4V p-p 3 1 Figure 14. AD8051/AD8052 Large Signal Frequency Response; G = +2 -20 0.01 100 VS = +5V VOUT = 2V p-p 4 2 01062-014 GAIN (dB) 8 0 10 FREQUENCY (MHz) 9 9 1 1 Figure 16. AD8054 0.1 dB Gain Flatness vs. Frequency; G = +2 Figure 13. AD8051/AD8052 0.1 dB Gain Flatness vs. Frequency; G = +2 2 VS = 5V RF = 200 RL = 150 G = +2 VOUT = 0.2V p-p 5.6 01062-017 5.4 5.8 PHASE MARGIN (Degrees) 5.5 VS = 5V G = +2 RL = 150 RF = 806 VOUT = 0.2V p-p 5.9 100k 1M 10M FREQUENCY (Hz) 100M 500M 01062-018 5.6 6.0 01062-016 6.0 01062-013 GAIN FLATNESS (dB) AD8051/AD8052/AD8054 Figure 18. AD8054 Open-Loop Gain and Phase Margin vs. Frequency Rev. J | Page 11 of 24 AD8051/AD8052/AD8054 VOUT = 2V p-p 1000 VS = 3V, G = -1 RF = 2k, RL = 100 -30 VOLTAGE NOISE (nV/Hz) VS = 5V, G = +2 RF = 2k, RL = 100 -40 VS = 5V, G = +1 RL = 100 -50 -60 -70 -80 VS = 5V, G = +2 RF = 2k, RL = 2k -90 VS = 5V, G = +1 RL = 2k VS = 5V 100 10 -110 1 2 3 4 5 6 FUNDAMENTAL FREQUENCY (MHz) 7 8 9 10 1 10 100 10M Figure 22. Input Voltage Noise vs. Frequency Figure 19. Total Harmonic Distortion 100 -30 VS = 5V -40 CURRENT NOISE (pA/Hz) 10MHz -50 WORST HARMONIC (dBc) 1M 1k 10k 100k FREQUENCY (Hz) 01062-022 -100 01062-019 TOTAL HARMONIC DISTORTION (dBc) -20 -60 -70 -80 5MHz -90 -100 1MHz VS = 5V RL = 2k G = +2 -110 -120 10 1 1.0 1.5 2.0 2.5 3.0 3.5 OUTPUT VOLTAGE (V p-p) 4.0 4.5 5.0 0.1 10 20 30 40 50 60 70 80 DIFFERENTIAL GAIN ERROR (%) 90 100 RL = 1k RL = 150 VS = 5V, G = +2 RF = 2k, RL AS SHOWN 0 10 20 30 40 50 60 70 80 MODULATING RAMP LEVEL (IRE) 90 100 DIFFERENTIAL PHASE ERROR (Degrees) 10 1M 10M NTSC SUBSCRIBER (3.58MHz) RL = 1k 0.05 0.00 -0.05 -0.10 01062-021 DIFFERENTIAL GAIN ERROR (%) DIFFERENTIAL PHASE ERROR (Degrees) 0 -0.05 -0.10 -0.15 -0.20 -0.25 RL = 1k VS = 5V, G = +2 RF = 2k, RL AS SHOWN 0.10 0.05 0.00 0.10 RL = 150 NTSC SUBSCRIBER (3.58MHz) 1k 10k 100k FREQUENCY (Hz) Figure 23. Input Current Noise vs. Frequency Figure 20. Worst Harmonic vs. Output Voltage 0.10 0.08 0.06 0.04 0.02 0.00 -0.02 -0.04 -0.06 100 VS = 5V, G = +2 RF = 2k, RL AS SHOWN RL = 150 1ST 2ND 3RD 4TH 5TH 6TH 7TH 8TH 9TH 10TH 11TH 0.3 0.2 0.1 RL = 1k 0.0 -0.1 -0.2 -0.3 VS = 5V, G = +2 RF = 2k, RL AS SHOWN RL = 150 1ST 2ND 3RD 4TH 5TH 6TH 7TH 8TH 9TH 10TH 11TH MODULATING RAMP LEVEL (IRE) Figure 24. AD8054 Differential Gain and Phase Errors Figure 21. AD8051/AD8052 Differential Gain and Phase Errors Rev. J | Page 12 of 24 01062-024 0.5 0 01062-020 -140 01062-023 -130 AD8051/AD8052/AD8054 -10 -10 VS = 5V RF = 2k RL = 2k VOUT = 2V p-p -20 -30 -40 -40 CROSSTALK (dB) -50 -60 -70 -60 -70 -90 -90 10 FREQUENCY (MHz) 100 500 -110 0.1 01062-025 1 Figure 25. AD8052 Crosstalk (Output-to-Output) vs. Frequency 1 100 500 Figure 28. AD8054 Crosstalk (Output-to-Output) vs. Frequency 0 20 VS = 5V 10 0 -30 -10 -40 -20 -50 -60 -80 -60 -90 -70 500 -80 0.01 01062-026 100 +PSRR -40 -70 1 10 FREQUENCY (MHz) -PSRR -30 -50 0.1 VS = 5V 0.1 100.000 500 70 VS =5V G = +1 SETTLING TIME TO 0.1% (ns) 60 10.000 3.100 1.000 0.310 0.100 VS = 5V G = -1 RL = 2k 50 AD8051/AD8052 40 AD8054 30 20 10 1 10 FREQUENCY (MHz) 100 500 01062-027 0.031 0.010 0.1 100 Figure 29. PSRR vs. Frequency Figure 26. CMRR vs. Frequency 31.000 1 10 FREQUENCY (MHz) 01062-029 PSRR (dB) -20 -100 0.03 OUTPUT RESISTANCE () 10 FREQUENCY (MHz) 01062-028 -100 -100 0.1 CMRR (dB) RL = 1k -80 -80 -10 RL = 100 -50 Figure 27. Closed-Loop Output Resistance vs. Frequency 0 0.5 1.0 1.5 INPUT STEP (V p-p) Figure 30. Settling Time vs. Input Step Rev. J | Page 13 of 24 2.0 01062-030 CROSSTALK (dB) -30 VS = 5V RF = 1k RL = AS SHOWN VOUT = 2V p-p -20 AD8051/AD8052/AD8054 1.000 VS = 5V 0.8 OUTPUT SATURATION VOLTAGE (V) 0.9 VOH = +85C VOH = +25C 0.7 VOH = -40C VOL = +85C 0.6 0.5 0.4 0.3 VOL = +25C 0.2 VOL = -40C 0.1 0 0 5 10 15 20 25 30 35 40 45 50 55 60 65 70 75 80 85 LOAD CURRENT (mA) 100 90 RL = 150 80 70 VS = 5V 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 OUTPUT VOLTAGE (V) 4.0 4.5 5.0 01062-032 OPEN-LOOP GAIN (dB) RL = 2k 60 0.750 Figure 32. Open-Loop Gain vs. Output Voltage Rev. J | Page 14 of 24 +5V - VOH (+25C) 0.625 +5V - VOH (-40C) 0.500 0.375 0.250 VOL (+125C) 0.125 0 Figure 31. AD8051/AD8052 Output Saturation Voltage vs. Load Current +5V - VOH (+125C) 0.875 VOL (-40C) 0 3 6 9 VOL (+25C) 12 15 18 21 LOAD CURRENT (mA) 24 27 30 Figure 33. AD8054 Output Saturation Voltage vs. Load Current 01062-033 VS = 5V 01062-031 OUTPUT SATURATION VOLTAGE (V) 1.0 AD8051/AD8052/AD8054 20ns 2.5 1V Figure 34. 100 mV Step Response, G = +1 Figure 37. Output Swing; G = -1, RL = 2 k VS = 5V G = +1 RL = 2k VS = 5V G = +1 RL = 2k 2.55 VOLTS 2.5 20ns 01062-035 50mV 50mV Figure 35. AD8051/AD8052 200 mV Step Response; VS = 5 V, G = +1 Figure 38. AD8054 100 mV Step Response; VS = 5 V, G = +1 VIN = 1V p-p G = +2 RL = 2k VS = 5V VS = 5V G = +1 RL = 2k 4 3 VOLTS 2 2.5 1 -1 -2 1.5 -3 0.5 500mV 20ns -4 01062-036 VOLTS 40ns 01062-038 2.45 2.4 3.5 2.50 Figure 36. Large Signal Step Response; VS = 5 V, G = +2 1V 20ns Figure 39. Large Signal Step Response; VS = 5 V, G = +1 Rev. J | Page 15 of 24 01062-039 VOLTS 2.6 4.5 2s 01062-037 VOLTS 1.5 20mV VS = 5V G = -1 RF = 2k RL = 2k 5.0 01062-034 VOLTS VIN = 0.1V p-p G = +1 RL = 2k VS = 3V AD8051/AD8052/AD8054 THEORY OF OPERATION The inputs of the device can handle voltages from -0.2 V below the negative rail to within 1 V of the positive rail. Exceeding these values do not cause phase reversal; however, the input ESD devices begin to conduct if the input voltages exceed the rails by greater than 0.5 V. During this overdrive condition, the output stays at the rail. CIRCUIT DESCRIPTION The AD8051/AD8052/AD8054 are fabricated on the Analog Devices, Inc. proprietary eXtra-Fast Complementary Bipolar (XFCB) process, which enables the construction of PNP and NPN transistors with similar fTs in the 2 GHz to 4 GHz region. The process is dielectrically isolated to eliminate the parasitic and latch-up problems caused by junction isolation. These features allow the construction of high frequency, low distortion amplifiers with low supply currents. This design uses a differential output input stage to maximize bandwidth and headroom (see Figure 40). The smaller signal swings required on the first stage outputs (nodes SIP, SIN) reduce the effect of nonlinear currents due to junction capacitances and improve the distortion performance. This design achieves harmonic distortion of -80 dBc @ 1 MHz into 100 with VOUT = 2 V p-p (gain = +1) on a single 5 V supply. The rail-to-rail output range of the AD8051/AD8052/AD8054 is provided by a complementary common emitter output stage. High output drive capability is provided by injecting all output stage predriver currents directly into the bases of the output devices Q8 and Q36. Biasing of Q8 and Q36 is accomplished by I8 and I5, along with a common-mode feedback loop (not shown). This circuit topology allows the AD8051/AD8052 to drive 45 mA of output current and allows the AD8054 to drive 30 mA of output current with the outputs within 0.5 V of the supply rails. VCC I10 Q4 R39 I2 Q51 R23 R27 I5 Q21 Q2 VOUT Q27 C9 SIN Q8 Q11 Q3 R5 VEE C3 Q31 Q7 VINN C7 Q39 Q23 Q22 Q1 SIP I9 Q50 Q36 Q5 VEE Q13 Q25 Q40 R15 R2 VINP I3 Q24 R21 R3 Q47 I11 I7 VEE Figure 40. AD8051/AD8052 Simplified Schematic Rev. J | Page 16 of 24 I8 VCC 01062-045 R26 AD8051/AD8052/AD8054 APPLICATION INFORMATION OVERDRIVE RECOVERY Overdrive of an amplifier occurs when the output and/or input range is exceeded. The amplifier must recover from this overdrive condition. As shown in Figure 41, the AD8051/AD8052/ AD8054 recover within 60 ns from negative overdrive and within 45 ns from positive overdrive. VOLTS VS = 5V G = +5 RF = 2k RL = 2k 2.55 2.50 2.45 2.40 100ns 50mV VOLTS OUTPUT 2V/DIV 2.60 01062-042 INPUT 1V/DIV VS = 5V G = +1 RL = 2k CL = 50pF Figure 43. AD8051/AD8052 200 mV Step Response; CL = 50 pF 10000 Consider the AD8051/AD8052 in a closed-loop gain of +1 with +VS = 5 V and a load of 2 k in parallel with 50 pF. Figure 42 and Figure 43 show their frequency and time domain responses, respectively, to a small-signal excitation. The capacitive load drive of the AD8051/AD8052/AD8054 can be increased by adding a low value resistor in series with the load. Figure 44 and Figure 45 show the effect of a series resistor on the capacitive drive for varying voltage gains. As the closed-loop gain is increased, the larger phase margin allows for larger capacitive loads with less peaking. Adding a series resistor with lower closed-loop gains accomplishes the same effect. For large capacitive loads, the frequency response of the amplifier is dominated by the roll-off of the series resistor and the load capacitance. RG 1 2 2 -4 6 RS = 10 RS = 0 100 RG VIN 100mV STEP 10 VS = 5V G = +1 RL = 2k CL = 50pF VOUT = 200mV p-p 1 2 RF RS VOUT CL 50 3 4 5 6 ACL (V/V) Figure 45. AD8054 Capacitive Load Drive vs. Closed-Loop Gain 10 FREQUENCY (MHz) 100 500 01062-041 1 5 VS = 5V 30% OVERSHOOT -2 -12 0.1 4 1000 0 -8 3 Figure 44. AD8051/AD8052 Capacitive Load Drive vs. Closed-Loop Gain 4 -10 VOUT CL 50 ACL (V/V) 6 -6 RF RS VIN 100mV STEP 10 1 8 GAIN (dB) 100 01062-043 DRIVING CAPACITIVE LOADS RS = 0 Figure 42. AD8051/AD8052 Closed-Loop Frequency Response; CL = 50 pF Rev. J | Page 17 of 24 01062-044 Figure 41. Overdrive Recovery RS = 3 1000 CAPACITIVE LOAD (pF) 100ns CAPACITIVE LOAD (pF) 01062-040 V/DIV AS SHOWN VS = 5V 30% OVERSHOOT AD8051/AD8052/AD8054 The specified high speed performance of the AD8051/AD8052/ AD8054 requires careful attention to board layout and component selection. Proper RF design techniques and low parasitic component selection are necessary. The PCB should have a ground plane covering all unused portions of the component side of the board to provide a low impedance path. The ground plane should be removed from the area near the input pins to reduce parasitic capacitance. Chip capacitors should be used for supply bypassing. One end should be connected to the ground plane and the other within 3 mm of each power pin. An additional large (4.7 F to 10 F) tantalum electrolytic capacitor should be connected in parallel, but not necessarily so close, to supply current for fast, large signal changes at the output. noise bandwidth of the analog signal before analog-to-digital conversion. Note that the unused amplifier's inputs should be tied to ground. R6 1k C1 50pF VIN R1 3k R2 2k R4 2k 2 1 R3 2k 6 7 3 R5 2k 14 12 9 5 AD8054 13 C2 50pF 8 10 AD8054 AD8054 BAND-PASS FILTER OUTPUT Figure 46. 2 MHz Biquad Band-Pass Filter Using AD8054 The frequency response of the circuit is shown in Figure 47. 0 The feedback resistor should be located close to the inverting input pin to keep the parasitic capacitance at this node to a minimum. Parasitic capacitance of less than 1 pF at the inverting input can significantly affect high speed performance. GAIN (dB) Stripline design techniques should be used for long signal traces (greater than about 25 mm). These should be designed with a characteristic impedance of 50 or 75 and be properly terminated at each end. -10 -20 -30 ACTIVE FILTERS Figure 46 shows an example of a 2 MHz biquad bandwidth filter that uses three op amps of an AD8054. Such circuits are sometimes used in medical ultrasound systems to lower the Rev. J | Page 18 of 24 -40 10k 100k 1M FREQUENCY (Hz) 10M 100M 01062-047 Active filters at higher frequencies require wider bandwidth op amps to work effectively. Excessive phase shift produced by lower frequency op amps can significantly affect active filter performance. Figure 47. Frequency Response of 2 MHz Band-Pass Biquad Filter 01062-046 LAYOUT CONSIDERATIONS AD8051/AD8052/AD8054 reduced to -60.18 dB and the ADC operated with 8.46 ENOBs as shown in Figure 49. The inclusion of the AD8051 in the circuit did not worsen the distortion performance of the AD9201. Figure 50 is a schematic showing the AD8051 used as a driver for an AD9201, a 10-bit, 20 MSPS, dual analog-to-digital converter. This converter is designed to convert I and Q signals in communications systems. In this application, only the I channel is being driven. The I channel is enabled by applying a logic high to SELECT (Pin 13). 10 AD8051 2 AMPLITUDE (dB) 54.97 -50 ENOB 8.80 SINAD 54.76 SFDR 71.66 -60 2ND -74.53 3RD -76.06 4TH -76.35 5TH -79.05 6TH -80.36 7TH -75.08 -110 8TH -88.12 -120 9TH -77.87 -70 2ND 0 1 2 3 4 5 6 7 FREQUENCY (MHz) 8 9 10 0 FCLK 20.0MHz FUND 9.5MHz VIN -0.44dB -30 THD -57.08 SNR 54.65 -40 -50 SINAD 52.69 ENOB 8.46 2ND -60 -70 3RD 4TH 6TH 7TH 8TH 5TH SFDR 60.18 2ND -60.18 3RD -60.23 -82.01 4TH -90 5TH 6TH -78.83 -100 7TH -77.28 -110 8TH -84.54 9TH -92.78 -120 0 1 2 3 4 5 6 7 FREQUENCY (MHz) 8 9 -81.28 10 Figure 49. FFT Plot for AD8051 Driving the AD9201 at 9.5 MHz 10pF 22 0.1F 10F 10F +5V 10F 0.1F 10F INA-I 17 INB-I 18 REFT-I D9 12 19 REFB-I D8 11 20 AVSS D7 10 21 REFSENSE D6 9 22 VREF D5 8 23 AVDD 24 REFB-Q D2 5 25 REFT-Q D1 4 26 INB-Q SELECT 13 +VDD AD9201 DATA OUT D4 7 1k 0.1F SLEEP 16 0.1F 0.1F CLOCK 14 15 0.1F 0.1F D3 6 D0 3 22 10pF 22 10pF DVSS 1 27 INA-Q 28 CHIP-SELECT Figure 50. The AD8051 Driving an AD9201, a 10-Bit, 20 MSPS Analog-to-Digital Converter Rev. J | Page 19 of 24 +5V DVDD 2 0.1F 10F 01062-050 AMPLITUDE (dB) PART# -20 0.1F -5V 9TH -10 10pF 10F 8TH FFTSIZE 8192 1k 0.1F 6TH FUND -80 6 4 5TH 7TH 0 0.01F 22 4TH 10 22 1k 3RD 01062-048 50 SNR Figure 48. FFT Plot for AD8051 Driving the AD9201 at 1 MHz 0.33F 3 -68.13 -40 -100 Figure 48 shows the FFT response of the ADC for the case of a 1 MHz analog input. The SFDR is 71.66 dB, and the analog-todigital is producing 8.8 ENOB (effective number of bits). When the analog frequency was raised to 9.5 MHz, the SFDR was 7 -0.51dB THD -90 With the sampling clock running at 20 MSPS, the analog-todigital output was analyzed with a digital analyzer. Two input frequencies were used, 1 MHz and 9.5 MHz, which is just short of the Nyquist frequency. These signals were well filtered to minimize any harmonics. 10F VIN -30 -80 The output of the op amp is ac-coupled into INA-I (Pin 16) via two parallel capacitors to provide good high frequency and low frequency coupling. The 1 k resistor references the signal to VREF that is applied to INB-I. Thus, INA-I swings both positive and negative with respect to the bias voltage applied to INB-I. 0.1F FUND 998.5kHz -20 The AD9201 has differential inputs for each channel. These are designated the A and B inputs. The B inputs of each channel are connected to VREF (Pin 22), which supplies a positive reference of 2.5 V. Each of the B inputs has a small low-pass filter that also helps to reduce distortion. 0 FFTSIZE 8192 FCLK 20.0MHz -10 The AD8051 is running from a dual supply and is configured for a gain of +2. The input signal is terminated in 50 and the output is 2 V p-p, which is the maximum input range of the AD9201. The 22 series resistor limits the maximum current that flows and helps to lower the distortion of the ADC. +5V PART# FUND 0 01062-049 ANALOG-TO-DIGITAL AND DIGITAL-TO-ANALOG APPLICATIONS AD8051/AD8052/AD8054 SYNC STRIPPER Synchronizing pulses are sometimes carried on video signals so as not to require a separate channel to carry the synchronizing information. However, for some functions, such as analog-todigital conversion, it is not desirable to have the sync pulses on the video signal. These pulses reduce the dynamic range of the video signal and do not provide any useful information for such a function. A sync stripper removes the synchronizing pulses from a video signal while passing all the useful video information. Figure 51 shows a practical single-supply circuit that uses only a single AD8051. It is capable of directly driving a reverse terminated video line. VIDEO WITHOUT SYNC VBLANK GROUND 3V OR 5V 0.1F VIN Some circuits use a sync tip clamp to hold the sync tips at a relatively constant level to lower the amount of dynamic signal swing required. However, these circuits can have artifacts, such as sync tip compression, unless they are driven by a source with a very low output impedance. The AD8051/AD8052/AD8054 have adequate signal swing when running on a single 5 V supply to handle an ac-coupled composite video signal. + 10F 7 3 AD8051 2 TO A/D 6 100 4 The other extreme is for a full white video signal. The blanking intervals and sync tips of such a signal have negative-going excursions in compliance with the composite video specifications. The combination of horizontal and vertical blanking intervals limit such a signal to being at the highest (white) level for a maximum of about 75% of the time. As a result of the duty cycles between the two extremes previously presented, a 1 V p-p composite video signal that is multiplied by a gain of 2 requires about 3.2 V p-p of dynamic voltage swing at the output for an op amp to pass a composite video signal of arbitrarily varying duty cycle without distortion. GROUND 0.4V The worst case of composite video is not quite this demanding. One bounding condition is a signal that is mostly black for an entire frame but has a white (full amplitude) minimum width spike at least once in a frame. R2 1k 01062-051 R1 1k 0.8V (OR 2 x VBLANK ) Figure 51. Sync Stripper The video signal plus sync is applied to the noninverting input with the proper termination. The amplifier gain is set to 2 via the two 1 k resistors in the feedback circuit. A bias voltage must be applied to R1 so that the input signal has the sync pulses stripped at the proper level. The blanking level of the input video pulse is the desired place to remove the sync information. This level is multiplied by 2 by the amplifier. This level must be at ground at the output for the sync stripping action to take place. Since the gain of the amplifier from the input of R1 to the output is -1, a voltage equal to 2 x VBLANK must be applied to make the blanking level come out at ground. SINGLE-SUPPLY COMPOSITE VIDEO LINE DRIVER Many composite video signals have their blanking level at ground and have video information that is both positive and negative. Such signals require dual-supply amplifiers to pass them. However, by ac level shifting, a single-supply amplifier can be used to pass these signals. The following complications can arise from such techniques. The input to the circuit in Figure 52 is a standard composite (1 V p-p) video signal that has the blanking level at ground. The input network level shifts the video signal by means of ac coupling. The noninverting input of the op amp is biased to half of the supply voltage. The feedback circuit provides unity gain for the dc-biasing of the input and provides a gain of 2 for any signals that are in the video bandwidth. The output is ac-coupled and terminated to drive the line. The capacitor values were selected for providing minimum tilt or field time distortion of the video signal. These values would be required for video that is considered to be studio or broadcast quality. However, if a lower consumer grade of video, sometimes referred to as consumer video, is all that is desired, the values and the cost of the capacitors can be reduced by as much as a factor of five with minimum visible degradation in the picture. 5V 4.99k 4.99k COMPOSITE VIDEO IN RT 75 Signals of bounded peak-to-peak amplitude that vary in duty cycle require larger dynamic swing capacity than their (bounded) peak-to-peak amplitude after they are ac-coupled. As a worst case, the dynamic signal swing will approach twice the peak-topeak value. The two conditions that define the maximum Rev. J | Page 20 of 24 47F + + 10F 0.1F 7 3 AD8051 10k 2 6 4 RF 1k + 10F 1000F + RBT 75 0.1F RL 75 VOUT RG 1k 220F Figure 52. Single-Supply Composite Video Line Driver 01062-052 VIDEO WITH SYNC dynamic swing requirements are a signal that is mostly low but goes high with a duty cycle that is a small fraction of a percent, and the other extreme defined by the opposite condition. AD8051/AD8052/AD8054 OUTLINE DIMENSIONS 8.75 (0.3445) 8.55 (0.3366) 8 14 1 6.20 (0.2441) 5.80 (0.2283) 7 1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0039) COPLANARITY 0.10 0.50 (0.0197) 0.25 (0.0098) 1.75 (0.0689) 1.35 (0.0531) SEATING PLANE 0.51 (0.0201) 0.31 (0.0122) 8 0 1.27 (0.0500) 0.40 (0.0157) 0.25 (0.0098) 0.17 (0.0067) COMPLIANT TO JEDEC STANDARDS MS-012-AB CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 53. 14-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-14) Dimensions shown in millimeters and (inches) 2.90 BSC 5 4 2.80 BSC 1.60 BSC 1 2 3 PIN 1 0.95 BSC 1.90 BSC 1.30 1.15 0.90 1.45 MAX 0.15 MAX 0.50 0.30 45 0.22 0.08 SEATING PLANE 10 5 0 COMPLIANT TO JEDEC STANDARDS MO-178-A A Figure 54. 5-Lead Small Outline Transistor Package [SOT-23] (RJ-5) Dimensions shown in millimeters Rev. J | Page 21 of 24 0.60 0.45 0.30 060606-A 4.00 (0.1575) 3.80 (0.1496) AD8051/AD8052/AD8054 3.20 3.00 2.80 8 3.20 3.00 2.80 5.15 4.90 4.65 5 1 4 PIN 1 0.65 BSC 0.95 0.85 0.75 1.10 MAX 0.15 0.00 0.38 0.22 COPLANARITY 0.10 0.80 0.60 0.40 8 0 0.23 0.08 SEATING PLANE COMPLIANT TO JEDEC STANDARDS MO-187-AA Figure 55. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters 5.00 (0.1968) 4.80 (0.1890) 5 1 6.20 (0.2441) 5.80 (0.2284) 4 1.27 (0.0500) BSC 1.75 (0.0688) 1.35 (0.0532) 0.25 (0.0098) 0.10 (0.0040) 0.51 (0.0201) 0.31 (0.0122) COPLANARITY 0.10 SEATING PLANE 0.50 (0.0196) 0.25 (0.0099) 45 8 0 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) COMPLIANT TO JEDEC STANDARDS MS-012-A A CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. 012407-A 8 4.00 (0.1574) 3.80 (0.1497) Figure 56. 8-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-8) Dimensions shown in millimeters and (inches) 5.10 5.00 4.90 14 8 4.50 4.40 4.30 6.40 BSC 1 7 PIN 1 0.65 BSC 1.20 MAX 0.15 0.05 COPLANARITY 0.10 0.30 0.19 0.20 0.09 SEATING PLANE 8 0 COMPLIANT TO JEDEC STANDARDS MO-153-AB-1 Figure 57. 14-Lead Thin Shrink Small Outline Package [TSSOP] (RU-14) Dimensions shown in millimeters Rev. J | Page 22 of 24 0.75 0.60 0.45 061908-A 1.05 1.00 0.80 AD8051/AD8052/AD8054 ORDERING GUIDE Model AD8051AR AD8051AR-REEL AD8051AR-REEL7 AD8051ARZ1 AD8051ARZ-REEL1 AD8051ARZ-REEL71 AD8051ART-R2 AD8051ART-REEL AD8051ART-REEL7 AD8051ARTZ-R21 AD8051ARTZ-REEL1 AD8051ARTZ-REEL71 AD8052AR AD8052AR-REEL AD8052AR-REEL7 AD8052ARZ1 AD8052ARZ-REEL1 AD8052ARZ-REEL71 AD8052ARM AD8052ARM-REEL AD8052ARM-REEL7 AD8052ARMZ1 AD8052ARMZ-REEL71 AD8054AR AD8054AR-REEL AD8054AR-REEL7 AD8054ARZ1 AD8054ARZ-REEL1 AD8054ARZ-REEL71 AD8054ARU AD8054ARU-REEL AD8054ARU-REEL7 AD8054ARUZ1 AD8054ARUZ-REEL1 AD8054ARUZ-REEL71 1 Temperature Range -40C to +125C -40C to +125C -40C to +125C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C Package Description 8-Lead SOIC_N 8-Lead SOIC_N, 13" Tape and Reel 8-Lead SOIC_N, 7" Tape and Reel 8-Lead SOIC_N 8-Lead SOIC_N, 13" Tape and Reel 8-Lead SOIC_N, 7" Tape and Reel 5-Lead SOT-23, 7" Tape and Reel 5-Lead SOT-23, 13" Tape and Reel 5-Lead SOT-23, 7" Tape and Reel 5-Lead SOT-23, 7" Tape and Reel 5-Lead SOT-23, 13" Tape and Reel 5-Lead SOT-23, 7" Tape and Reel 8-Lead SOIC_N 8-Lead SOIC_N, 13" Tape and Reel 8-Lead SOIC_N, 7" Tape and Reel 8-Lead SOIC_N 8-Lead SOIC_N, 13" Tape and Reel 8-Lead SOIC_N, 7" Tape and Reel 8-Lead MSOP 8-Lead MSOP, 13" Tape and Reel 8-Lead MSOP, 7" Tape and Reel 8-Lead MSOP 8-Lead MSOP, 7" Tape and Reel 14-Lead SOIC_N 14-Lead SOIC_N, 13" Tape and Reel 14-Lead SOIC_N, 7" Tape and Reel 14-Lead SOIC_N 14-Lead SOIC_N, 13" Tape and Reel 14-Lead SOIC_N, 7" Tape and Reel 14-Lead TSSOP 14-Lead TSSOP, 13" Tape and Reel 14-Lead TSSOP, 7" Tape and Reel 14-Lead TSSOP 14-Lead TSSOP, 13" Tape and Reel 14-Lead TSSOP, 7" Tape and Reel Z = RoHS Compliant Part. # denotes lead-free product may be top or bottom marked. Rev. J | Page 23 of 24 Package Option R-8 R-8 R-8 R-8 R-8 R-8 RJ-5 RJ-5 RJ-5 RJ-5 RJ-5 RJ-5 R-8 R-8 R-8 R-8 R-8 R-8 RM-8 RM-8 RM-8 RM-8 RM-8 R-14 R-14 R-14 R-14 R-14 R-14 RU-14 RU-14 RU-14 RU-14 RU-14 RU-14 Branding H2A H2A H2A H06 H06 H06 H4A H4A H4A H4A# H4A# AD8051/AD8052/AD8054 NOTES (c)2009 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D01062-0-7/09(J) Rev. J | Page 24 of 24