www.power.com August 2016
TNY263-268
TinySwitch-II Family
Enhanced, Energy Efcient, Low Power
Off-line Switcher
This Product is Covered by Patents and/or Pending Patent Applications.
This product is not recommended for new designs.
Figure 1. Typical Standby Application.
Product Highlights
TinySwitch-II Features Reduce System Cost
• Fully integrated auto-restart for short circuit and open loop fault
protection – saves external component costs
• Built-in circuitry practically eliminates audible noise with ordinary
dip-varnished transformer
• Programmable line undervoltage detect feature prevents power
on/off glitches – saves external components
• Frequency jittering dramatically reduces EMI (~10 dB)
– minimizes EMI filter component costs
• 132 kHz operation reduces transformer size – allows use of
EF12.6 or EE13 cores for low cost and small size
• Very tight tolerances and negligible temperature variation on key
parameters eases design and lowers cost
• Lowest component count switcher solution
• Expanded scalable device family for low system cost
Better Cost/Performance over RCC & Linears
• Lower system cost than RCC, discrete PWM and other
integrated/hybrid solutions
• Cost effective replacement for bulky regulated linears
• Simple ON/OFF control – no loop compensation needed
• No bias winding – simpler, lower cost transformer
• Simple design practically eliminates rework in manufacturing
EcoSmart™– Extremely Energy Efficient
• No load consumption <50 mW with bias winding and
<250 mW without bias winding at 265 VAC input
• Meets California Energy Commission (CEC), Energy Star, and
EU requirements
• Ideal for cell-phone charger and PC standby applications
High Performance at Low Cost
• High voltage powered – ideal for charger applications
• High bandwidth provides fast turn on with no overshoot
• Current limit operation rejects line frequency ripple
• Built-in current limit and thermal protection improves safety
Description
TinySwitch™-II integrates a 700 V power MOSFET, oscillator,
high voltage switched current source, current limit and thermal
shutdown circuitry onto a monolithic device. The start-up and
operating power are derived directly from the voltage on the
DRAIN pin, eliminating the need for a bias winding and associated
circuitry. In addition, the TinySwitch-II devices incorporate
auto-restart, line undervoltage sense, and frequency jittering. An
innovative design minimizes audio frequency components in the
simple ON/OFF control scheme to practically eliminate audible
noise with standard taped/varnished transformer construction.
PI-2684-061815
Wide-Range
High-Voltage
DC Input D
S
EN/UV
BP
+
-
+
-
DC
Output
TinySwitch-II
Optional
UV Resistor
The fully integrated auto-restart circuit safely limits output power
during fault conditions such as output short circuit or open loop,
reducing component count and secondary feedback circuitry
cost. An optional line sense resistor externally programs a line
undervoltage threshold, which eliminates power down glitches
caused by the slow discharge of input storage capacitors present
in applications such as standby supplies. The operating
frequency of 132 kHz is jittered to significantly reduce both the
quasi-peak and average EMI, minimizing filtering cost.
Output Power Table
Product3
230 VAC ± 15% 85-265 VAC
Adapter1Open
Frame2Adapter1Open
Frame2
TNY263 P/G 5 W 7.5 W 3.7 W 4.7 W
TNY264 P/G 5.5 W 9 W 4 W 6 W
TNY265 P/G 8.5 W 11 W 5.5 W 7.5 W
TNY266 P/G 10 W 15 W 6 W 9.5 W
TNY267 P/G 13 W 19 W 8 W 12 W
TNY268 P/G 16 W 23 W 10 W 15 W
Table 1. Output Power Table.
Notes:
1. Minimum continuous power in a typical non-ventilated enclosed adapter
measured at 50 °C ambient.
2. Minimum practical continuous power in an open frame design with adequate
heat sinking, measured at 50 °C ambient (See Key Applications
Considerations).
3. Packages: P: DIP-8B, G: SMD-8B. Please see Part Ordering Information.
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Figure 2. Functional Block Diagram.
Figure 3. Pin Configuration.
Pin Functional Description
DRAIN (D) Pin:
Power MOSFET drain connection. Provides internal operating
current for both start-up and steady-state operation.
BYPASS (BP) Pin:
Connection point for a 0.1 µF external bypass capacitor for the
internally generated 5.8 V supply.
ENABLE/UNDERVOLTAGE (EN/UV) Pin:
This pin has dual functions: enable input and line undervoltage
sense. During normal operation, switching of the power
MOSFET is controlled by this pin. MOSFET switching is
terminated when a current greater than 240 µA is drawn from
this pin. This pin also senses line undervoltage conditions
through an external resistor connected to the DC line voltage.
If there is no external resistor connected to this pin,
TinySwitch-II detects its absence and disables the line
undervoltage function.
SOURCE (S) Pin:
Control circuit common, internally connected to output
MOSFET source.
SOURCE (HV RTN) Pin:
Output MOSFET source connection for high voltage return.
PI-2643-031715
CLOCK
OSCILLATOR
5.8 V
4.8 V
SOURCE
(S)
S
R
Q
DCMAX
BYPASS
(BP)
+
-
VILIMIT
FAULT
PRESENT
CURRENT LIMIT
COMPARATOR
ENABLE
LEADING
EDGE
BLANKING
THERMAL
SHUTDOWN
+
-
DRAIN
(D)
REGULATOR
5.8 V
BYPASS PIN
UNDERVOLTAGE
1.0 V + VT
ENABLE/
UNDER-
VOLTAGE
(EN/UV)
Q
240 µA 50 µA
LINE UNDERVOLTAGE
RESET
AUTO-
RESTART
COUNTER
JITTER
1.0 V
6.3 V
CURRENT
LIMIT STATE
MACHINE
PI-2685-031715
EN/UV D
S
S
S (HV RTN)
S (HV RTN)
BP
P Package (DIP-8B)
G Package (SMD-8B)
8
5
7
1
4
2
3
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Figure 4. Frequency Jitter.
TinySwitch-II Functional Description
TinySwitch-II combines a high voltage power MOSFET switch
with a power supply controller in one device. Unlike conventional
PWM (pulse width modulator) controllers, TinySwitch-II uses a
simple ON/OFF control to regulate the output voltage.
The TinySwitch-II controller consists of an oscillator, enable
circuit (sense and logic), current limit state machine,
5.8 V regulator, BYPASS pin undervoltage circuit, over-
temperature protection, current limit circuit, leading edge
blanking and a 700 V power MOSFET. TinySwitch-II
incorporates additional circuitry for line undervoltage sense,
auto-restart and frequency jitter. Figure 2 shows the functional
block diagram with the most important features.
Oscillator
The typical oscillator frequency is internally set to an average
of 132 kHz. Two signals are generated from the oscillator: the
maximum duty cycle signal (DCMAX) and the clock signal that
indicates the beginning of each cycle.
The TinySwitch-II oscillator incorporates circuitry that
introduces a small amount of frequency jitter, typically 8 kHz
peak-to-peak, to minimize EMI emission. The modulation rate
of the frequency jitter is set to 1 kHz to optimize EMI reduction
for both average and quasi-peak emissions. The frequency
jitter should be measured with the oscilloscope triggered at
the falling edge of the DRAIN waveform. The waveform in
Figure 4 illustrates the frequency jitter of the TinySwitch-II.
Enable Input and Current Limit State Machine
The enable input circuit at the EN/UV pin consists of a low
impedance source follower output set at 1.0 V. The current
through the source follower is limited to 240 µA. When the
current out of this pin exceeds 240 µA, a low logic level
(disable) is generated at the output of the enable circuit. This
enable circuit output is sampled at the beginning of each cycle
on the rising edge of the clock signal. If high, the power
MOSFET is turned on for that cycle (enabled). If low, the power
MOSFET remains off (disabled). Since the sampling is done
only at the beginning of each cycle, subsequent changes in
the EN/UV pin voltage or current during the remainder of the
cycle are ignored.
The current limit state machine reduces the current limit by
discrete amounts at light loads when TinySwitch-II is likely to
switch in the audible frequency range. The lower current limit
raises the effective switching frequency above the audio range
and reduces the transformer flux density, including the
associated audible noise. The state machine monitors the
sequence of EN/UV pin voltage levels to determine the load
condition and adjusts the current limit level accordingly in
discrete amounts.
Under most operating conditions (except when close to no-
load), the low impedance of the source follower keeps the
voltage on the EN/UV pin from going much below 1.0 V in the
disabled state. This improves the response time of the
optocoupler that is usually connected to this pin.
5.8 V Regulator and 6.3 V Shunt Voltage Clamp
The 5.8 V regulator charges the bypass capacitor connected
to the BYPASS pin to 5.8 V by drawing a current from the
voltage on the DRAIN pin whenever the MOSFET is off. The
BYPASS pin is the internal supply voltage node for the
TinySwitch-II. When the MOSFET is on, the TinySwitch-II
operates from the energy stored in the bypass capacitor.
Extremely low power consumption of the internal circuitry
allows TinySwitch-II to operate continuously from current it
takes from the DRAIN pin. A bypass capacitor value of 0.1 µF
is sufficient for both high frequency decoupling and energy
storage.
In addition, there is a 6.3 V shunt regulator clamping the
BYPASS pin at 6.3 V when current is provided to the BYPASS
pin through an external resistor. This facilitates powering of
TinySwitch-II externally through a bias winding to decrease the
no-load consumption to about 50 mW.
BYPASS Pin Undervoltage
The BYPASS pin undervoltage circuitry disables the power
MOSFET when the BYPASS pin voltage drops below 4.8 V.
Once the BYPASS pin voltage drops below 4.8 V, it must rise
back to 5.8 V to enable (turn-on) the power MOSFET.
Over Temperature Protection
The thermal shutdown circuitry senses the die temperature.
The threshold is typically set at 135 °C with 70 °C hysteresis.
When the die temperature rises above this threshold the
power MOSFET is disabled and remains disabled until the die
temperature falls by 70 °C, at which point it is re-enabled. A
large hysteresis of 70 °C (typical) is provided to prevent
overheating of the PC board due to a continuous fault
condition.
Current Limit
The current limit circuit senses the current in the power
MOSFET. When this current exceeds the internal threshold
(ILIMIT), the power MOSFET is turned off for the remainder of
600
0510
136 kHz
128 kHz
VDRAIN
Time (µs)
PI-2741-041901
500
400
300
200
100
0
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Figure 5. TinySwitch-II Auto-Restart Operation.
PI-2699-030701
01000 2000
Time (ms)
0
5
0
10
100
200
300
VDRAIN
VDC-OUTPUT
that cycle. The current limit state machine reduces the current
limit threshold by discrete amounts under medium and light
loads.
The leading edge blanking circuit inhibits the current limit
comparator for a short time (tLEB) after the power MOSFET is
turned on. This leading edge blanking time has been set so
that current spikes caused by capacitance and secondary-
side rectifier reverse recovery time will not cause premature
termination of the switching pulse.
Auto-Restart
In the event of a fault condition such as output overload,
output short circuit, or an open loop condition, TinySwitch-II
enters into auto-restart operation. An internal counter clocked
by the oscillator gets reset every time the EN/UV pin is pulled
low. If the EN/UV pin is not pulled low for 50 ms, the power
MOSFET switching is normally disabled for 850 ms (except in
the case of line undervoltage condition, in which case it is
disabled until the condition is removed). The auto-restart
alternately enables and disables the switching of the power
MOSFET until the fault condition is removed. Figure 5
illustrates auto-restart circuit operation in the presence of an
output short circuit.
In the event of a line undervoltage condition, the switching of
the power MOSFET is disabled beyond its normal 850 ms time
until the line undervoltage condition ends.
Line Undervoltage Sense Circuit
The DC line voltage can be monitored by connecting an
external resistor from the DC line to the EN/UV pin. During
power-up or when the switching of the power MOSFET is
disabled in auto-restart, the current into the EN/UV pin must
exceed 49 µA to initiate switching of the power MOSFET.
During power-up, this is accomplished by holding the BYPASS
pin to 4.8 V while the line undervoltage condition exists. The
BYPASS pin then rises from 4.8 V to 5.8 V when the line
undervoltage condition goes away. When the switching of the
power MOSFET is disabled in auto-restart mode and a line
undervoltage condition exists, the auto-restart counter is
stopped. This stretches the disable time beyond its normal
850 ms until the line undervoltage condition ends.
The line undervoltage circuit also detects when there is no
external resistor connected to the EN/UV pin (less than
~2 µA into the pin). In this case the line undervoltage function
is disabled.
TinySwitch-II Operation
TinySwitch-II devices operate in the current limit mode. When
enabled, the oscillator turns the power MOSFET on at the
beginning of each cycle. The MOSFET is turned off when the
current ramps up to the current limit or when the DCMAX limit is
reached. Since the highest current limit level and frequency of
a TinySwitch-II design are constant, the power delivered to the
load is proportional to the primary inductance of the transformer
and peak primary current squared. Hence, designing the supply
involves calculating the primary inductance of the transformer
for the maximum output power required. If the TinySwitch-II is
appropriately chosen for the power level, the current in the
calculated inductance will ramp up to current limit before the
DCMAX limit is reached.
Enable Function
TinySwitch-II senses the EN/UV pin to determine whether or
not to proceed with the next switching cycle as described
earlier. The sequence of cycles is used to determine the
current limit. Once a cycle is started, it always completes the
cycle (even when the EN/UV pin changes state half way
through the cycle). This operation results in a power supply in
which the output voltage ripple is determined by the output
capacitor, amount of energy per switch cycle and the delay of
the feedback.
The EN/UV pin signal is generated on the secondary by
comparing the power supply output voltage with a reference
voltage. The EN/UV pin signal is high when the power supply
output voltage is less than the reference voltage.
In a typical implementation, the EN/UV pin is driven by an
optocoupler. The collector of the optocoupler transistor is
connected to the EN/UV pin and the emitter is connected to
the SOURCE pin. The optocoupler LED is connected in series
with a Zener diode across the DC output voltage to be
regulated. When the output voltage exceeds the target
regulation voltage level (optocoupler LED voltage drop plus
Zener voltage), the optocoupler LED will start to conduct,
pulling the EN/UV pin low. The Zener diode can be replaced
by a TL431 reference circuit for improved accuracy.
ON/OFF Operation with Current Limit State Machine
The internal clock of the TinySwitch-II runs all the time. At the
beginning of each clock cycle, it samples the EN/UV pin to
decide whether or not to implement a switch cycle, and based
on the sequence of samples over multiple cycles, it determines
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V
DRAIN
V
EN
CLOCK
D
DRAIN
I
MAX
Figure 6. TinySwitch-II Operation at Near Maximum Loading.
V
DRAIN
V
EN
CLOCK
D
DRAIN
I
MAX
Figure 8. TinySwitch-II Operation at Medium Loading.
V
DRAIN
V
EN
CLOCK
D
DRAIN
I
MAX
Figure 7. TinySwitch-II Operation at Moderately Heavy Loading.
the appropriate current limit. At high loads, when the EN/UV
pin is high (less than 240 µA out of the pin), a switching cycle
with the full current limit occurs. At lighter loads, when EN/UV
is high, a switching cycle with a reduced current limit occurs.
At near maximum load, TinySwitch-II will conduct during
nearly all of its clock cycles (Figure 6). At slightly lower load, it
will “skip” additional cycles in order to maintain voltage
regulation at the power supply output (Figure 7). At medium
loads, cycles will be skipped and the current limit will be
reduced (Figure 8). At very light loads, the current limit will be
reduced even further (Figure 9). Only a small percentage of
cycles will occur to satisfy the power consumption of the
power supply.
The response time of the TinySwitch-II ON/OFF control
scheme is very fast compared to normal PWM control. This
provides tight regulation and excellent transient response.
Power Up/Down
The TinySwitch-II requires only a 0.1 µF capacitor on the
BYPASS pin. Because of its small size, the time to charge this
capacitor is kept to an absolute minimum, typically 0.6 ms.
Due to the fast nature of the ON/OFF feedback, there is no
overshoot at the power supply output. When an external
resistor (2 MΩ) is connected from the positive DC input to the
EN/UV pin, the power MOSFET switching will be delayed
during power-up until the DC line voltage exceeds the
threshold (100 V). Figures 10 and 11 show the power-up timing
waveform of TinySwitch-II in applications with and without an
external resistor (2 MΩ) connected to the EN/UV pin.
During power-down, when an external resistor is used, the
power MOSFET will switch for 50 ms after the output loses
regulation. The power MOSFET will then remain off without
any glitches since the undervoltage function prohibits restart
when the line voltage is low.
Figure 12 illustrates a typical power-down timing waveform of
TinySwitch-II. Figure 13 illustrates a very slow power-down
timing waveform of TinySwitch-II as in standby applications.
The external resistor (2 MΩ) is connected to the EN/UV pin in
this case to prevent unwanted restarts.
The TinySwitch-II does not require a bias winding to provide
power to the chip, because it draws the power directly from
the DRAIN pin (see Functional Description above). This has
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Figure 12. Normal Power-down Timing (without UV).
Figure 13. Slow Power-down Timing with Optional External
(2 MΩ) UV Resistor Connected to EN/UV Pin.
Figure 10. TinySwitch-II Power-up with Optional External UV
Resistor (2 MΩ) Connected to EN/UV Pin.
Figure 11. TinySwitch-II Power-up without Optional External UV
Resistor Connected to EN/UV Pin.
V
DRAIN
V
EN
CLOCK
D
DRAIN
I
MAX
Figure 9. TinySwitch-II Operation at Very Light Load.
two main benefits. First, for a nominal application, this
eliminates the cost of a bias winding and associated
components. Secondly, for battery charger applications, the
current-voltage characteristic often allows the output voltage
to fall close to zero volts while still delivering power. This type
of application normally requires a forward-bias winding which
has many more associated components. With TinySwitch-II,
neither are necessary. For applications that require a very low
no-load power consumption (50 mW), a resistor from a bias
winding to the BYPASS pin can provide the power to the chip.
The minimum recommended current supplied is 750 µA. The
BYPASS pin in this case will be clamped at 6.3 V. This method
will eliminate the power draw from the DRAIN pin, thereby
PI-2395-101014
02.5 5
0
100
200
400
300
0
100
200
VDC-INPUT
VDRAIN
01 2
Time (ms)
0
200
400
5
0
10
0
100
200
PI-2383-021015
VDC-INPUT
VBYPASS
VDRAIN
PI-2381-021015
01 2
Time (ms)
0
200
400
5
0
10
0
100
200
VDC-INPUT
VBYPASS
VDRAIN
PI-2348-021015
0.5 1
Time (s)
0
100
200
300
0
100
200
400
VDC-INPUT
VDRAIN
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Figure 14. 2.5 W Constant Voltage, Constant Current Battery Charger with Universal Input (85-265 VAC).
PI-2706-061815
+ 5 V
500 mA
RTN
D1
1N4005
C1
3.3 µF
400 V
Fusible
RF1
8.2 Ω
C3
0.1 µF
C7
10 µF
10 V
85-265
VAC
L1
2.2 mH
D2
1N4005
D3
1N4005 D4
1N4005
R2
200 kΩ
U2
LTV817
D5
1N5819
Shield
L2
3.3 µH
C5
330 µF
16 V
C2
3.3 µF
400 V
C6
100 µF
35 V
R7
100 Ω
R4
1.2 Ω
1/2 W
Q1
2N3904
R8
270 Ω
VR1
BZX79B3V9
3.9 V
U1
TNY264
C3
2.2 nF
D6
1N4937
R6
1 Ω
1/2 W
T1
R1
1.2 kΩ
1 8
4 5
R3
22 Ω
R9
47 Ω
C8 680 pF
Y1 Safety
TinySwitch-II
D
S
BP
EN/UV
reducing the no-load power consumption and improving full-
load efficiency.
Current Limit Operation
Each switching cycle is terminated when the DRAIN current
reaches the current limit of the TinySwitch-II. Current limit
operation provides good line ripple rejection and relatively
constant power delivery independent of input voltage.
BYPASS Pin Capacitor
The BYPASS pin uses a small 0.1 µF ceramic capacitor for
decoupling the internal power supply of the TinySwitch-II.
Application Examples
The TinySwitch-II is ideal for low cost, high efficiency power
supplies in a wide range of applications such as cellular phone
chargers, PC standby, TV standby, AC adapters, motor
control, appliance control and ISDN or a DSL network
termination. The 132 kHz operation allows the use of a low
cost EE13 or EF12.6 core transformer while still providing good
efficiency. The frequency jitter in TinySwitch-II makes it
possible to use a single inductor (or two small resistors for
under 3 W applications if lower efficiency is acceptable) in
conjunction with two input capacitors for input EMI filtering.
The auto-restart function removes the need to oversize the
output diode for short circuit conditions allowing the design to
be optimized for low cost and maximum efficiency. In charger
applications, it eliminates the need for a second optocoupler
and Zener diode for open loop fault protection. Auto-restart
also saves the cost of adding a fuse or increasing the power
rating of the current sense resistors to survive reverse battery
conditions. For applications requiring undervoltage lock out
(UVLO), such as PC standby, the TinySwitch-II eliminates
several components and saves cost. TinySwitch-II is well
suited for applications that require constant voltage and
constant current output. As TinySwitch-II is always powered
from the input high voltage, it therefore does not rely on bias
winding voltage. Consequently this greatly simplifies designing
chargers that must work down to zero volts on the output.
2.5 W CV/CC Cell-Phone Charger
As an example, Figure 14 shows a TNY264 based 5 V,
0.5 A, cellular phone charger operating over a universal input
range (85 VAC to 265 VAC). The inductor (L1) forms a π-filter
in conjunction with C1 and C2. The resistor R1 damps
resonances in the inductor L1. Frequency jittering operation of
TinySwitch-II allows the use of a simple π-filter described
above in combination with a single low value Y1-capacitor (C8)
to meet worldwide conducted EMI standards. The addition of
a shield winding in the transformer allows conducted EMI to be
met even with the output capacitively earthed (which is the
worst case condition for EMI). The diode D6, capacitor C3
and resistor R2 comprise the clamp circuit, limiting the leakage
inductance turn-off voltage spike on the TinySwitch-II DRAIN
pin to a safe value. The output voltage is determined by the
sum of the optocoupler U2 LED forward drop (~1 V), and Zener
diode VR1 voltage. Resistor R8 maintains a bias current
through the Zener diode to ensure it is operated close to the
Zener test current.
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up undervoltage threshold is set at 200 VDC, slightly below the
lowest required operating DC input voltage, for start-up at 170
VAC, with doubler. This feature saves several components
needed to implement the glitch-free turn-off compared with
discrete or TinySwitch-II based designs. During turn-on the
rectified DC input voltage needs to exceed 200 V undervoltage
threshold for the power supply to start operation. But, once the
power supply is on it will continue to operate down to
140 V rectified DC input voltage to provide the required hold up
time for the standby output.
The auxiliary primary side winding is rectified and filtered by D2
and C2 to create a 12 V primary bias output voltage for the
main power supply primary controller. In addition, this voltage is
used to power the TinySwitch-II via R4. Although not necessary
for operation, supplying the TinySwitch-II externally reduces the
device quiescent dissipation by disabling the internal drain
derived current source normally used to keep the BYPASS pin
capacitor (C3) charged. An R4 value of 10 kΩ provides 600 µA
into the BYPASS pin, which is slightly in excess of the current
consumption of TinySwitch-II. The excess current is safely
clamped by an on-chip active Zener diode to 6.3 V.
The secondary winding is rectified and filtered by D3 and C6.
For a 15 W design an additional output capacitor, C7, is
required due to the larger secondary ripple currents compared
to the 10 W standby design. The auto-restart function limits
output current during short circuit conditions, removing the
need to over rate D3. Switching noise filtering is provided by L1
and C8. The 5 V output is sensed by U2 and VR1. R5 is used to
ensure that the Zener diode is biased at its test current and R6
centers the output voltage at 5 V.
In many cases the Zener regulation method provides sufficient
accuracy (typically ± 6% over a 0 °C to 50 °C temperature
range). This is possible because TinySwitch-II limits the dynamic
range of the optocoupler LED current, allowing the Zener diode
to operate at near constant bias current. However, if higher
accuracy is required, a TL431 precision reference IC may be
used to replace VR1.
A simple constant current circuit is implemented using the VBE
of transistor Q1 to sense the voltage across the current sense
resistor R4. When the drop across R4 exceeds the VBE of
transistor Q1, it turns on and takes over control of the loop by
driving the optocoupler LED. Resistor R6 assures sufficient
voltage to keep the control loop in operation down to zero volts
at the output. With the output shorted, the drop across R4 and
R6 (~1.2 V) is sufficient to keep the Q1 and LED circuit active.
Resistors R7 and R9 limit the forward current that could be
drawn through VR1 by Q1 under output short circuit conditions,
due to the voltage drop across R4 and R6.
10 and 15 W Standby Circuits
Figures 15 and 16 show examples of circuits for standby
applications. They both provide two outputs: an isolated 5 V
and a 12 V primary referenced output. The first, using TNY266P,
provides 10 W, and the second, using TNY267P,
15 W of output power. Both operate from an input range of 140
VDC to 375 VDC, corresponding to a 230 VAC or 100/115 VAC
with doubler input. The designs take advantage of the line
undervoltage detect, auto-restart and higher switching
frequency of TinySwitch-II. Operation at 132 kHz allows the use
of a smaller and lower cost transformer core, EE16 for
10 W and EE22 for 15 W. The removal of pin 6 from the 8 pin
DIP TinySwitch-II packages provides a large creepage distance
which improves reliability in high pollution environments such as
fan cooled power supplies.
Capacitor C1 provides high frequency decoupling of the high
voltage DC supply, only necessary if there is a long trace length
from the DC bulk capacitors of the main supply. The line sense
resistors R2 and R3 sense the DC input voltage for line
undervoltage. When the AC is turned off, the undervoltage
detect feature of the TinySwitch-II prevents auto-restart glitches
at the output caused by the slow discharge of large storage
capacitance in the main converter. This is achieved by
preventing the TinySwitch-II from switching when the input
voltage goes below a level needed to maintain output
regulation, and keeping it off until the input voltage goes above
the undervoltage threshold, when the AC is turned on again.
With R2 and R3, giving a combined value of 2 MΩ, the power
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C1
0.01 µF
1 kV
140 - 375
VDC INPUT
L1
10 µH
2 A
R5
680 Ω
R6
59 Ω
1%
D3
1N5822
U1
TNY266P
C5
2.2 nF
1 kV
D1
1N4005GP
U2
TLP181Y
VR1
BZX79B3V9
5
4
2
110
8
TinySwitch-II
D
S
BP
+5 V, 2 A
RTN
C2
82 µF
35 V
C8
470 µF
10 V
PI-2713-061815
C4
1 nF Y1
D2
1N4148
EN
+12 VDC, 20 mA
0 V
C3
0.1 µF
50 V
R4
10 kΩ
C6
1000 µF
10 V
R2
1 MΩ
R3
1 MΩ
R1
200 kΩ
T1
PERFORMANCE SUMMARY
Continuous Output Power: 10.24 W
Efciency: ≥ 75%
Figure 16. 15 W Standby Supply.
C1
0.01 µF
1 kV
140 - 375
VDC INPUT
L1
10 µH
3 A
R5
680 Ω
D3
SB540
U1
TNY267P
C5
2.2 nF
1 kV
D1
1N4005GP
U2
TLP181Y
PERFORMANCE SUMMARY
Continuous Output Power: 15.24 W
Efciency: ≥ 78%
5
4
2
110
8
TinySwitch-II
D
S
BP
+5 V, 3 A
RTN
C2
82 µF
35 V
C8
470 µF
10 V
PI-2712-061815
C4
1 nF Y1
D2
1N4148
EN
+12 VDC, 20 mA
0 V
C3
0.1 µF
50 V
R4
10 kΩ
C7
1000 µF
10 V
C6
1000 µF
10 V
R2
1 MΩ
R3
1 MΩ
R1
100 kΩ
T1 R6
59 Ω
1%
VR1
BZX79B3V9
Figure 15. 10 W Standby Supply.
Rev. J 08/16
10
TNY263-268
www.power.com
Key Application Considerations
TinySwitch-II vs. TinySwitch
Table 2 compares the features and performance differences
between the TNY254 device of the TinySwitch-II family with
the TinySwitch-II family of devices. Many of the new features
eliminate the need for or reduce the cost of circuit components.
Other features simplify the design and enhance performance.
Design
Output Power
Table 1 (front page) shows the practical continuous output
power levels that can be obtained under the following
conditions:
Table 2. Comparison Between TinySwitch and TinySwitch-II.
*Not available. ** See typical performance curves.
1. The minimum DC input voltage is 90 V or higher for
85 VAC input, or 240 V or higher for 230 VAC input or
115 VAC input with a voltage doubler. This corresponds to
a filter capacitor of 3 µF/W for universal input and 1 µF/W
for 230 VAC or 115 VAC with doubler input.
2. A secondary output of 5 V with a Schottky rectifier diode.
3. Assumed efficiency of 77% (TNY267 & TNY268), 75%
(TNY265 & TNY266) and 73% (TNY263 & TNY264).
4. The parts are board mounted with SOURCE pins soldered
to sufficient area of copper to keep the die temperature at
or below 100 °C.
In addition to the thermal environment (sealed enclosure,
ventilated, open frame, etc.), the maximum power capability of
TinySwitch-II in a given application depends on transformer
TinySwitch-II vs. TinySwitch
Function TinySwitch
TNY254
TinySwitch-II
TNY263-268
TinySwitch-II
Advantages
Switching Frequency and
Tolerance
Temperature Variation
(0-100 °C)**
44 kHz ±10% (at 25 °C)
+8%
132 kHz ±6% (at 25 °C)
+2%
• Smaller transformer for low cost
• Ease of design
• Manufacturability
• Optimum design for lower cost
Active Frequency Jitter N/A* ±4 kHz • Lower EMI minimizing filter
component costs
Transformer Audible Noise
Reduction
N/A* Yes–built into controller • Practically eliminates audible noise with ordinary dip
varnished transformer – no special
construction or gluing required
Line UV Detect N/A* Single resistor
programmable
• Prevents power on/off glitches
Current Limit Tolerance
Temperature Variation
(0-100 °C)**
±11% (at 25 °C)
-8%
±7% (at 25 °C)
0%
• Increases power capability and
simplifies design for high volume
manufacturing
Auto-Restart N/A* 6% effective on-time • Limits output short-circuit current to less than full
load current
• No output diode size penalty
• Protects load in open loop fault conditions
• No additional components required
BYPASS Pin Zener Clamp N/A* Internally clamped to 6.3 V • Allows TinySwitch-II to be powered from a low
voltage bias winding to improve efficiency and to
reduce on-chip power dissipation
DRAIN Creepage at Package 0.037 in. / 0.94 mm 0.137 in. / 3.48 mm • Greater immunity to arcing as a result of dust,
debris or other contaminants build-up
Rev. J 08/16
11
TNY263-268
www.power.com
core size and design (continuous or discontinuous), efficiency,
minimum specified input voltage, input storage capacitance,
output voltage, output diode forward drop, etc., and can be
different from the values shown in Table 1.
Audible Noise
The TinySwitch-II practically eliminates any transformer audio
noise using simple ordinary varnished transformer construction.
No gluing of the cores is needed. The audio noise reduction is
accomplished by the TinySwitch-II controller reducing the
current limit in discrete steps as the load is reduced. This
minimizes the flux density in the transformer when switching at
audio frequencies.
Worst Case EMI & Efficiency Measurement
Since identical TinySwitch-II supplies may operate at several
different frequencies under the same load and line conditions,
care must be taken to ensure that measurements are made
under worst case conditions. When measuring efficiency or
EMI verify that the TinySwitch-II is operating at maximum
frequency and that measurements are made at both low and
high line input voltages to ensure the worst case result is
obtained.
Layout
Single Point Grounding
Use a single point ground connection at the SOURCE pin for
the BYPASS pin capacitor and the Input Filter Capacitor
(see Figure 17).
Primary Loop Area
The area of the primary loop that connects the input filter
capacitor, transformer primary and TinySwitch-II together
should be kept as small as possible.
Primary Clamp Circuit
A clamp is used to limit peak voltage on the DRAIN pin at turn-
off. This can be achieved by using an RCD clamp (as shown
in Figure 14). A Zener and diode clamp (200 V) across the
primary or a single 550 V Zener clamp from DRAIN to
SOURCE can also be used. In all cases care should be taken
to minimize the circuit path from the clamp components to the
transformer and TinySwitch-II.
Thermal Considerations
Copper underneath the TinySwitch-II acts not only as a single
point ground, but also as a heatsink. The hatched areas
shown in Figure 17 should be maximized for good heat sinking
of TinySwitch-II and the same applies to the output diode.
EN/UV pin
If a line undervoltage detect resistor is used then the resistor
should be mounted as close as possible to the EN/UV pin to
minimize noise pick up.
The voltage rating of a resistor should be considered for the
undervoltage detect (Figure 15: R2, R3) resistors. For 1/4 W
resistors, the voltage rating is typically 200 V continuous,
whereas for 1/2 W resistors the rating is typically 400 V
continuous.
Y-Capacitor
The placement of the Y-capacitor should be directly from the
primary bulk capacitor positive rail to the common/return
terminal on the secondary side. Such placement will maximize
the EMI benefit of the Y-capacitor and avoid problems in
common-mode surge testing.
Optocoupler
It is important to maintain the minimum circuit path from the
optocoupler transistor to the TinySwitch-II EN/UV and
SOURCE pins to minimize noise coupling.
The EN/UV pin connection to the optocoupler should be kept
to an absolute minimum (less than 12.7 mm or 0.5 in.), and
this connection should be kept away from the DRAIN pin
(minimum of 5.1 mm or 0.2 in.).
Output Diode
For best performance, the area of the loop connecting the
secondary winding, the output diode and the output filter
capacitor, should be minimized. See Figure 17 for optimized
layout. In addition, sufficient copper area should be provided
at the anode and cathode terminals of the diode for adequate
heatsinking.
Input and Output Filter Capacitors
There are constrictions in the traces connected to the input
and output filter capacitors. These constrictions are present
for two reasons. The first is to force all the high frequency
currents to flow through the capacitor (if the trace were wide
then it could flow around the capacitor). Secondly, the
Constrictions minimize the heat transferred from the TinySwitch-II
to the input filter capacitor and from the secondary diode to
the output filter capacitor. The common/return (the negative
output terminal in Figure 17) terminal of the output filter
capacitor should be connected with a short, low impedance
path to the secondary winding. In addition, the common/
return output connection should be taken directly from the
secondary winding pin and not from the Y-capacitor
connection point.
PC Board Cleaning
Power Integrations does not recommend the use of “no clean”
flux.
For the most up-to-date information visit the PI website
at: www.power.com.
Rev. J 08/16
12
TNY263-268
www.power.com
TOP VIEW
PI-2707-061815
Y1-
Capacitor
Opto-
coupler
D
EN/UV
BP
+
–
HV
+– DC
OUT
Input Filter Capacitor
Output Filter Capacitor
Safety Spacing
Maximize hatched copper
areas ( ) for optimum
heat sinking
S
S
SEC
C
BP
TinySwitch-II
PRI
T
r
a
n
s
f
o
r
m
e
r
Figure 17. Recommended Circuit Board Layout for TinySwitch-II with Undervoltage Lock Out Resistor.
Rev. J 08/16
13
TNY263-268
www.power.com
Parameter Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 18
(Unless Otherwise Specified)
Min Typ Max Units
Control Functions
Output Frequency fOSC
TJ = 25 °C
See Figure 4
Average 124 132 140
kHz
Peak-Peak Jitter 8
Maximum Duty Cycle DCMAX S1 Open 62 65 68 %
EN/UV Pin Turnoff
Threshold Current IDIS TJ = -40 °C to 125 °C -300 -240 -170 µA
EN/UV Pin Voltage VEN
IEN/UV = -125 µA 0.4 1.0 1.5
V
IEN/UV = 25 µA 1.3 2.3 2.7
DRAIN Supply Current
IS1 VEN/UV = 0 V 430 500 µA
IS2
EN/UV Open
(MOSFET
Switching)
See Note A, B
TNY263 200 250
µA
TNY264 225 270
TNY265 245 295
TNY266 265 320
TNY267 315 380
TNY268 380 460
BYPASS Pin Charge
Current
ICH1
VBP = 0 V,
TJ = 25 °C
See Note C, D
TNY263-264 -5.5 -3.3 -1.8
mA
TNY265-268 -7.5 -4.6 -2.5
ICH2
VBP = 4 V,
TJ = 25 °C
See Note C, D
TNY263-264 -3.8 -2.0 -1.0
TNY265-268 -4.5 -3.0 -1.5
Absolute Maximum Ratings(1,4)
DRAIN Voltage .................................. ................ -0.3 V to 700 V
DRAIN Peak Current: TNY263......................................400 mA
TNY264.....................................400 mA
.................................... TNY265......................................440 mA
TNY266.....................................560 mA
.................................... TNY267.....................................720 mA
TNY268.....................................880 mA
EN/UV Voltage ....................................................... -0.3 V to 9 V
EN/UV Current ............................................................... 100 mA
BYPASS Voltage .................................................. .. -0.3 V to 9 V
Storage Temperature ....................................... -65 °C to 150 °C
Operating Junction Temperature(2) .................... -40 °C to 150 °C
Lead Temperature(3) ....................................................... .. 260 °C
Notes:
1. All voltages referenced to SOURCE, TA = 25 °C.
2. Normally limited by internal circuitry.
3. 1/16 in. from case for 5 seconds.
4. Maximum ratings specified may be applied one at a time,
without causing permanent damage to the product.
Exposure to Absolute Maximum Rating conditions for
extended periods of time may affect product reliability.
Thermal Resistance
Thermal Resistance: P or G Package:
(qJA) ........................... 70 °C/W(2); 60 °C/W(3)
(qJC)(1) ............................................... 11 °C/W
Notes:
1. Measured on the SOURCE pin close to plastic interface.
2. Soldered to 0.36 sq. in. (232 mm2), 2 oz. (610 g/m2) copper clad.
3. Soldered to 1 sq. in. (645 mm2), 2 oz. (610 g/m2) copper clad.
Rev. J 08/16
14
TNY263-268
www.power.com
Parameter Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 18
(Unless Otherwise Specified)
Min Typ Max Units
Control Functions (cont.)
BYPASS Pin
Voltage VBP See Note C 5.6 5.85 6.15 V
BYPASS Pin
Voltage Hysteresis VBPH 0.80 0.95 1.20 V
EN/UV Pin Line Under-
Voltage Threshold ILUV TJ = 25 °C 44 49 54 µA
Circuit Protection
Current Limit ILIMIT
TNY263
TJ = 25 °C
di/dt = 42 mA/µs
See Note E 195 210 225
mA
TNY264
TJ = 25 °C
di/dt = 50 mA/µs
See Note E 233 250 267
TNY265
TJ = 25 °C
di/dt = 55 mA/µs
See Note E 255 275 295
TNY266
TJ = 25 °C
di/dt = 70 mA/µs
See Note E 325 350 375
TNY267
TJ = 25 °C
di/dt = 90 mA/µs
See Note E 419 450 481
TNY268
TJ = 25 °C
di/dt = 110 mA/µs
See Note E 512 550 588
Initial Current Limit IINIT
See Figure 21
TJ = 25 °C
0.65 x
ILIMIT(MIN)
mA
Leading Edge
Blanking Time tLEB
TJ = 25 °C
See Note F 170 215 ns
Current Limit
Delay tILD
TJ = 25 °C
See Note F, G 150 ns
Thermal Shutdown
Temperature 125 135 150 °C
Thermal Shutdown
Hysteresis 70 °C
Output
ON-State
Resistance RDS(ON)
TNY263
ID = 21 mA
TJ = 25 °C 33 38
Ω
TJ = 100 °C 50 57
TNY264
ID = 25 mA
TJ = 25 °C 28 32
TJ = 100 °C 42 48
TNY265
ID = 28 mA
TJ = 25 °C 19 22
TJ = 100 °C 29 33
Rev. J 08/16
15
TNY263-268
www.power.com
Parameter Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 18
(Unless Otherwise Specified)
Min Typ Max Units
Output (cont.)
ON-State
Resistance RDS(ON)
TNY266
ID = 35 mA
TJ = 25 °C 14 16
Ω
TJ = 100 °C 21 24
TNY267
ID = 45 mA
TJ = 25 °C 7.8 9.0
TJ = 100 °C 11.7 13.5
TNY268
ID = 55 mA
TJ = 25 °C 5.2 6.0
TJ = 100 °C 7.8 9.0
OFF-State Drain
Leakage Current IDSS
VBP = 6.2 V,
VEN/UV = 0 V,
VDS = 560 V,
TJ = 125 °C
TNY263-266 50
µA
TNY267-268 100
Breakdown
Voltage BVDSS
VBP = 6.2 V, VEN/UV = 0 V,
See Note H, TJ = 25 °C 700 V
Rise Time tRMeasured in a Typical Flyback
Converter Application
50 ns
Fall Time tF50 ns
Drain Supply
Voltage 50 V
Output EN/UV Delay tEN/UV See Figure 20 10 µs
Output Disable
Setup Time tDST 0.5 µs
Auto-Restart
ON-Time tAR
TJ = 25 °C
See Note I 50 ms
Auto-Restart
Duty Cycle DCAR 5.6 %
NOTES:
A. Total current consumption is the sum of IS1 and IDSS when EN/UV pin is shorted to ground (MOSFET not switching) and the sum of
IS2 and IDSS when EN/UV pin is open (MOSFET switching).
B. Since the output MOSFET is switching, it is difficult to isolate the switching current from the supply current at the DRAIN.
An alternative is to measure the BYPASS pin current at 6.1 V.
C. BYPASS pin is not intended for sourcing supply current to external circuitry.
D. See Typical Performance Characteristics section for BYPASS pin start-up charging waveform.
E. For current limit at other di/dt values, refer to Figure 25.
F. This parameter is derived from characterization.
G. This parameter is derived from the change in current limit measured at 1X and 4X of the di/dt shown in the ILIMIT specification.
H. Breakdown voltage may be checked against minimum BVDSS specification by ramping the DRAIN pin voltage up to but not
exceeding minimum BVDSS.
I. Auto-restart on-time has the same temperature characteristics as the oscillator (inversely proportional to frequency).
Rev. J 08/16
16
TNY263-268
www.power.com
Figure 19. TinySwitch-II Duty Cycle Measurement. Figure 20. TinySwitch-II Output Enable Timing.
Figure 18. TinySwitch-II General Test Circuit.
PI-2686-031715
0.1 µF
10 V
50 V
470 Ω
5 W S2
470 Ω
NOTE: This test circuit is not applicable for current limit or output characteristic measurements.
D EN/UV
BPS
S S
S
150 V
S1
2 MΩ
PI-2364-012699
EN/UV
tP
tEN/UV
DCMAX
tP = 1
fOSC
VDRAIN
(internal signal)
0.8
Figure 21. Current Limit Envelope.
Rev. J 08/16
17
TNY263-268
www.power.com
Typical Performance Characteristics
Figure 22. Breakdown vs. Temperature.
1.1
1.0
0.9
-50 -25 0255075 100 125 150
Junction Temperature (°C)
Breakdown Voltage
(Normalized to 25 °C)
PI-2213-012301
1.2
1.0
0.8
0.6
0.4
0.2
0
-50 -25 0255075 100 125
Junction Temperature (°C)
PI-2680-012301
Output Frequency
(Normalized to 25 °C)
6
5
4
3
2
1
0
0 0.2 0.4 0.6 0.8 1.0
Time (ms)
PI-2240-012301
BYPASS Pin Voltage (V)
7
Drain Voltage (V)
Drain Current (mA)
300
250
200
100
50
150
0
0 2 4 6 8 10
TCASE = 25 °C
TCASE = 100 °C
PI-2221-031715
TNY263 0.85
TNY264 1.0
TNY265 1.5
TNY266 2.0
TNY267 3.5
TNY268 5.5
Scaling Factors:
Figure 23. Frequency vs. Temperature.
Figure 24. Current Limit vs. Temperature.
Figure 25. Current Limit vs. di/dt.
Figure 26. BYPASS Pin Start-up Waveform.
Figure 27. Output Characteristic.
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
1234
Normalized di/dt
PI-2697-033104
Normalized Current Limit
TNY263 42 mA/ s 210 mA
TNY264 50 mA/ s 250 mA
TNY265 55 mA/ s 275 mA
TNY266 70 mA/ s 350 mA
TNY267 90 mA/ s 450 mA
TNY268 110 mA/ s 550 mA
Normalized
di/dt = 1
Normalized
Current
Limit = 1
1
0.8
0.6
0.4
0.2
0.0
-50 0 50 100 150
Temperature (°C)
PI-2714-031715
1.2
Current Limit
(Normalized to 25 °C)
TNY263/268
TNY264-266
TNY267
Rev. J 08/16
18
TNY263-268
www.power.com
Typical Performance Characteristics (cont.)
Drain Voltage (V)
Drain Capacitance (pF)
PI-2683-033104
0 100 200 300 400 500 600
1
10
100
1000
TNY263 1.0
TNY264 1.0
TNY265 1.5
TNY266 2.0
TNY267 3.5
TNY268 5.5
Scaling Factors:
35
20
25
30
5
10
15
0
0 200 400 600
Drain Voltage (V)
Power (mW)
PI-2225-031715
TNY263 1.0
TNY264 1.0
TNY265 1.5
TNY266 2.0
TNY267 3.5
TNY268 5.5
Scaling Factors:
Junction Temperature (°C)
PI-2698-012301
Under-Voltage Threshold
(Normalized to 25 °C)
Figure 28. COSS vs. Drain Voltage.
Figure 29. Drain Capacitance Power.
Figure 30. Under-voltage Threshold vs. Temperature.
Rev. J 08/16
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TNY263-268
www.power.com
Notes:
1. Package dimensions conform to JEDEC specification
MS-001-AB (Issue B 7/85) for standard dual-in-line (DIP)
package with .300 inch row spacing.
2. Controlling dimensions are inches. Millimeter sizes are
shown in parentheses.
3. Dimensions shown do not include mold flash or other
protrusions. Mold flash or protrusions shall not exceed
.006 (.15) on any side.
4. Pin locations start with Pin 1, and continue counter-clock-
wise to Pin 8 when viewed from the top. The notch and/or
dimple are aids in locating Pin 1. Pin 6 is omitted.
5. Minimum metal to metal spacing at the package body for
the omitted lead location is .137 inch (3.48 mm).
6. Lead width measured at package body.
7. Lead spacing measured with the leads constrained to be
perpendicular to plane T.
.008 (.20)
.015 (.38)
.300 (7.62) BSC
(NOTE 7)
.300 (7.62)
.390 (9.91)
.356 (9.05)
.387 (9.83)
.240 (6.10)
.260 (6.60)
.125 (3.18)
.145 (3.68)
.057 (1.45)
.068 (1.73)
.118 (3.00)
.140 (3.56)
.015 (.38)
MINIMUM
.048 (1.22)
.053 (1.35)
.100 (2.54) BSC
.014 (.36)
.022 (.56)
-E-
Pin 1
SEATING
PLANE
-D-
-T-
P08B
PDIP-8B (P Package)
PI-2551-081716
D S .004 (.10)
⊕
T E D S .010 (.25) M
⊕
(NOTE 6)
.137 (3.48)
MINIMUM
Rev. J 08/16
20
TNY263-268
www.power.com
SMD-8B (G Package)
PI-2546-081716
.004 (.10)
.012 (.30)
.036 (0.91)
.044 (1.12)
.004 (.10)
0 -
° 8°
.356 (9.05)
.387 (9.83)
.048 (1.22) .009 (.23)
.053 (1.35)
.032 (.81)
.037 (.94)
.125 (3.18)
.145 (3.68)
-D-
Notes:
1. Controlling dimensions are
inches. Millimeter sizes are
shown in parentheses.
2. Dimensions shown do not
include mold flash or other
protrusions. Mold flash or
protrusions shall not exceed
.006 (.15) on any side.
3. Pin locations start with Pin 1,
and continue counter-clock-
wise to Pin 8 when viewed
from the top. Pin 6 is omitted.
4. Minimum metal to metal
spacing at the package body
for the omitted lead location
is .137 inch (3.48 mm).
5. Lead width measured at
package body.
6. D and E are referenced
datums on the package body.
.057 (1.45)
.068 (1.73)
(NOTE 5)
E S
.100 (2.54) (BSC)
.372 (9.45)
.240 (6.10) .388 (9.86)
.137 (3.48)
MINIMUM
.260 (6.60)
.010 (.25)
-E-
Pin 1
D S .004 (.10)
⊕
⊕
G08B
.420
.046 .060 .060 .046
.080
Pin 1
.086
.186
.286
Solder Pad Dimensions
Part Ordering Information
• TinySwitch Product Family
• Series Number
• Package Identifier
G Plastic Surface Mount SMD-8B
P Plastic DIP-8B
• Lead Finish
Blank Standard (Sn Pb)
N Pure Matte Tin (RoHS Compliant)
G RoHS Compliant and Halogen Free (P package only)
• Tape & Reel and Other Options
Blank Standard Configurations
TL Tape & Reel, 1 k pcs minimum, G Package only.
TNY 264 G N - TL
Rev. J 08/16
21
TNY263-268
www.power.com
Revision Notes Date
A – 03/01
B
Corrected first page spacing and sentence in description describing innovative design.
Corrected Frequency Jitter in Figure 4 and Frequency Jitter in Parameter Table.
Added last sentence to Over Temperature Protection section.
Clarified detecting when there is no external resistor connected to the EN/UV pin.
Corrected Figure 6 and its description in the text.
Corrected formatting, grammar and style errors in text and figures.
Corrected and moved Worst Case EMI & Efficiency Measurement section.
Added PC Board Cleaning section.
Replaced Figure 21 and SMD-8B Package Drawing.
07/01
C
Corrected qJA for P/G package.
Updated Figures 15 and 16 and text description for Zener performance.
Corrected DIP-8B and SMD-8B Package Drawings.
04/03
D Corrected EN/UV under-voltage threshold in text.
Corrected 2 MW connected between positive DC input to EN/UV pin in text and Figures 15 and 16. 03/04
E Added TNY263 and TNY265. 04/04
F Added lead-free ordering information. 12/04
G
1) Typographical correction in OFF-STATE Drain Leakage Current parameter condition.
2) Removed IDS condition from BVDSS parameter and added new Note H.
3) Added Note 4 to Absolute Maximum Ratings specifications.
04/05
H Reformatted document, updated Figures 23 and 24 and Part Ordering Information. 02/09
I Updated with new Brand Style. 06/15
JUpdated PDIP-8B (P Package) and SMD-8B (G Package) per PCN-16232. 08/16
For the latest updates, visit our website: www.power.com
Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability. Power
Integrations does not assume any liability arising from the use of any device or circuit described herein. POWER INTEGRATIONS
MAKES NO WARRANTY HEREIN AND SPECIFICALLY DISCLAIMS ALL WARRANTIES INCLUDING, WITHOUT LIMITATION, THE
IMPLIED WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE, AND NON-INFRINGEMENT OF THIRD
PARTY RIGHTS.
Patent Information
The products and applications illustrated herein (including transformer construction and circuits external to the products) may be
covered by one or more U.S. and foreign patents, or potentially by pending U.S. and foreign patent applications assigned to Power
Integrations. A complete list of Power Integrations patents may be found at www.power.com. Power Integrations grants its customers
a license under certain patent rights as set forth at http://www.power.com/ip.htm.
Life Support Policy
POWER INTEGRATIONS PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES
OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF POWER INTEGRATIONS. As used herein:
1. A Life support device or system is one which, (i) is intended for surgical implant into the body, or (ii) supports or sustains life, and (iii)
whose failure to perform, when properly used in accordance with instructions for use, can be reasonably expected to result in
significant injury or death to the user.
2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to
cause the failure of the life support device or system, or to affect its safety or effectiveness.
The PI logo, TOPSwitch, TinySwitch, SENZero, SCALE-iDriver, Qspeed, PeakSwitch, LYTSwitch, LinkZero, LinkSwitch, InnoSwitch,
HiperTFS, HiperPFS, HiperLCS, DPA-Switch, CAPZero, Clampless, EcoSmart, E-Shield, Filterfuse, FluxLink, StakFET, PI Expert and
PI FACTS are trademarks of Power Integrations, Inc. Other trademarks are property of their respective companies. ©2016, Power
Integrations, Inc.
World Headquarters
5245 Hellyer Avenue
San Jose, CA 95138, USA.
Main: +1-408-414-9200
Customer Service:
Phone: +1-408-414-9665
Fax: +1-408-414-9765
e-mail: usasales@power.com
China (Shanghai)
Rm 2410, Charity Plaza, No. 88
North Caoxi Road
Shanghai, PRC 200030
Phone: +86-21-6354-6323
Fax: +86-21-6354-6325
e-mail: chinasales@power.com
China (Shenzhen)
17/F, Hivac Building, No. 2, Keji
Nan 8th Road, Nanshan District,
Shenzhen, China, 518057
Phone: +86-755-8672-8689
Fax: +86-755-8672-8690
e-mail: chinasales@power.com
Germany
Lindwurmstrasse 114
80337 Munich
Germany
Phone: +49-895-527-39110
Fax: +49-895-527-39200
e-mail: eurosales@power.com
Germany
HellwegForum 1
59469 Ense
Germany
Tel: +49-2938-64-39990
e-mail: igbt-driver.sales@
power.com
India
#1, 14th Main Road
Vasanthanagar
Bangalore-560052 India
Phone: +91-80-4113-8020
Fax: +91-80-4113-8023
e-mail: indiasales@power.com
Italy
Via Milanese 20, 3rd. Fl.
20099 Sesto San Giovanni (MI)
Italy
Phone: +39-024-550-8701
Fax: +39-028-928-6009
e-mail: eurosales@power.com
Japan
Kosei Dai-3 Bldg.
2-12-11, Shin-Yokohama,
Kohoku-ku
Yokohama-shi, Kanagawa
222-0033 Japan
Phone: +81-45-471-1021
Fax: +81-45-471-3717
e-mail: japansales@power.com
Korea
RM 602, 6FL
Korea City Air Terminal B/D, 159-6
Samsung-Dong, Kangnam-Gu,
Seoul, 135-728, Korea
Phone: +82-2-2016-6610
Fax: +82-2-2016-6630
e-mail: koreasales@power.com
Singapore
51 Newton Road
#19-01/05 Goldhill Plaza
Singapore, 308900
Phone: +65-6358-2160
Fax: +65-6358-2015
e-mail: singaporesales@power.com
Taiwan
5F, No. 318, Nei Hu Rd., Sec. 1
Nei Hu Dist.
Taipei 11493, Taiwan R.O.C.
Phone: +886-2-2659-4570
Fax: +886-2-2659-4550
e-mail: taiwansales@power.com
UK
Cambridge Semiconductor,
a Power Integrations company
Westbrook Centre, Block 5,
2nd Floor
Milton Road
Cambridge CB4 1YG
Phone: +44 (0) 1223-446483
e-mail: eurosales@power.com
Power Integrations Worldwide Sales Support Locations