REV. B
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties that
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices.
a
OP37
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700 www.analog.com
Fax: 781/326-8703 © Analog Devices, Inc., 2002
Low Noise, Precision, High Speed
Operational Amplifier (A
VCL
> 5)
SIMPLIFIED SCHEMATIC
V–
V+
Q2B
R2*
Q3
Q2AQ1A Q1B
R4
R1*
R3 18
VOS ADJ.
R1 AND R2 ARE PERMANENTLY
ADJUSTED AT WAFER TEST FOR
MINIMUM OFFSET VOLTAGE.
*
NON-INVERTING
INPUT (+)
INVERTING
INPUT (–)
Q6
Q21
C2
R23 R24
Q23 Q24
Q22
R5
Q11 Q12
Q27 Q28
C1
R9
R12
C3 C4
Q26
Q20 Q19
Q46
Q45
OUTPUT
FEATURES
Low Noise, 80 nV p-p (0.1 Hz to 10 Hz)
3 nV/÷Hz @ 1 kHz
Low Drift, 0.2 V/C
High Speed, 17 V/s Slew Rate
63 MHz Gain Bandwidth
Low Input Offset Voltage, 10 V
Excellent CMRR, 126 dB (Common-Voltage @ 11 V)
High Open-Loop Gain, 1.8 Million
Replaces 725, OP-07, SE5534 In Gains > 5
Available in Die Form
GENERAL DESCRIPTION
The OP37 provides the same high performance as the OP27,
but the design is optimized for circuits with gains greater than
five. This design change increases slew rate to 17 V/ms and
gain-bandwidth product to 63 MHz.
The OP37 provides the low offset and drift of the OP07
plus higher speed and lower noise. Offsets down to 25 mV and
a
maximum drift
of 0.6 mV/∞C make the OP37 ideal for preci-
sion
instrumentation applications. Exceptionally low noise
(e
n
=
3.5 nV/ @ 10 Hz), a low 1/f noise corner frequency of
2.7 Hz,
and the high gain of 1.8 million, allow accurate
high-gain amplification of low-level signals.
The low input bias current of 10 nA and offset current of 7 nA
are achieved by using a bias-current cancellation circuit.
Over
the military temperature range this typically holds I
B
and I
OS
to 20 nA and 15 nA respectively.
PIN CONNECTIONS
8-Lead Hermetic DIP
(Z Suffix)
Epoxy Mini-DIP
(P Suffix)
8-Lead SO
(S Suffix)
8
7
6
5
1
2
3
4
NC = NO CONNECT
V
OS
TRIM
–IN
+IN
V
OS
TRIM
V+
OUT
NCV–
OP37
The output stage has good load driving capability. A guaranteed
swing of 10 V into 600 W and low output distortion make the
OP37 an excellent choice for professional audio applications.
PSRR and CMRR exceed 120 dB. These characteristics, coupled
with long-term drift of 0.2 mV/month, allow the circuit
designer
to achieve performance levels previously attained only by
discrete designs.
Low-cost, high-volume production of the OP37 is achieved
by
using on-chip zener-zap trimming. This reliable and stable
offset
trimming scheme has proved its effectiveness over many
years of
production history.
The OP37 brings low-noise instrumentation-type performance
to
such diverse applications as microphone, tapehead, and RIAA
phono preamplifiers, high-speed signal conditioning for data
acquisition systems, and wide-bandwidth instrumentation.
REV. B
OP37
–2–
ABSOLUTE MAXIMUM RATINGS
4
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 V
Internal Voltage (Note 1 ) . . . . . . . . . . . . . . . . . . . . . . . . . 22 V
Output Short-Circuit Duration . . . . . . . . . . . . . . . . . Indefinite
Differential Input Voltage (Note2) . . . . . . . . . . . . . . . . . 0.7 V
Differential Input Current (Note 2) . . . . . . . . . . . . . . . . 25 mA
Storage Temperature Range . . . . . . . . . . . . . –65∞C to +150∞C
Operating Temperature Range
OP37A . . . . . . . . . . . . . . . . . . . . . . . . . . . . –55∞C to +125∞C
OP37E (Z) . . . . . . . . . . . . . . . . . . . . . . . . . . –25∞C to +85∞C
OP37E, OP-37F (P) . . . . . . . . . . . . . . . . . . . . . 0∞C to 70∞C
OP37G (P, S, Z) . . . . . . . . . . . . . . . . . . . . . –40∞C to +85∞C
Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300∞C
Junction Temperature . . . . . . . . . . . . . . . . . . –45∞C to +150∞C
Package Type
JA3
JC
Unit
8-Lead Hermetic DIP (Z) 148 16 ∞C/W
8-Lead Plastic DIP (P) 103 43 ∞C/W
8-Lead SO (S) 158 43 ∞C/W
NOTES
1
For supply voltages less than 22 V, the absolute maximum input voltage is equal
to the supply voltage.
2
The OP37’s inputs are protected by back-to-back diodes. Current limiting resistors
are not used in order to achieve low noise. If differential input voltage exceeds 0.7 V,
the input Current should be limited to 25 mA.
3
JA
is specified for worst case mounting conditions, i.e.,
JA
is specified for device
in socket for TO, CerDIP, P-DIP, and LCC packages;
JA
is specified for device
soldered to printed circuit board for SO package.
4
Absolute maximum ratings apply to both DICE and packaged parts, unless
otherwise noted.
ORDERING GUIDE
T
A
= 25∞COperating
V
OS
MAX CerDIP Plastic Temperature
(V) 8-Lead 8-Lead Range
25 OP37AZ*MIL
25 OP37EZ OP37EP IND/COM
60 OP37FP*IND/COM
100 OP37GP XIND
100 OP37GZ OP37GS XIND
*Not for new design, obsolete, April 2002.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although
the OP37 features proprietary ESD protection circuitry, permanent damage may occur on
devices subjected to high-energy electrostatic discharges. Therefore, proper ESD precautions
are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
REV. B –3–
OP37
SPECIFICATIONS
( VS = 15 V, TA = 25C, unless otherwise noted.)
OP37A/E OP37F OP37G
Parameter Symbol Conditions Min Typ Max Min Typ Max Min Typ Max Unit
Input Offset
Voltage V
OS
Note 1 10 25 20 60 30 100 mV
Long-Term
Stability V
OS
/Time Notes 2, 3 0.2 1.0 0.3 1.5 0.4 2.0 mV/Mo
Input Offset
Current I
OS
735 950 12 75 nA
Input Bias
Current I
B
±10 ±40 ±12 ±55 ±15 ±80 nA
Input Noise
Voltage e
np-p
1 Hz to 10 Hz
3, 5
0.08 0.18 0.08 0.18 0.09 0.25 mV p-p
Input Noise
Voltage Density e
n
f
O
= 10 Hz
3
3.5 5.5 3.5 5.5 3.8 8.0
f
O
= 30 Hz
3
3.1 4.5 3.1 4.5 3.3 5.6 nV/÷ Hz
f
O
= 1000 Hz
3
3.0 3.8 3.0 3.8 3.2 4.5
Input Noise
Current Density i
N
f
O
= 10 Hz
3, 6
1.7 4.0 1.7 4.0 1.7
f
O
= 30 Hz
3, 6
1.0 2.3 1.0 2.3 1.0 pA/÷ Hz
f
O
= 1000 Hz
3, 6
0.4 0.6 0.4 0.6 0.4 0.6
Input Resistance
Differential
Mode R
IN
Note 7 1.3 6 0.9 4 5 0.7 4 MW
Input Resistance
Common Mode
R
INCM
32.5 2 GW
Input Voltage
Range IVR ±11 ±12.3 ±11 ±12.3 ±11 ±12.3 V
Common Mode
Rejection Ratio
CMRR V
CM
= ±11 V 114 126 106 123 100 120 dB
Power Supply
Rejection Ratio
PSSR V
S
= ±4 V 1 10 1 10 2 20 mV/ V
to ±18 V
Large Signal
Voltage Gain A
VO
R
L
≥ 2 kW,
V
O
= ±10 V 1000 1800 1000 1800 700 1500 V/mV
R
L
≥ 1 kW,
Vo = ±10 V 800 1500 800 1500 400 1500 V/mV
R
L
≥ 600 W,
V
O
= ±1 V,
V
S
±4
4
250 700 250 700 200 500 V/mV
Output Voltage
Swing V
O
R
L
≥ 2 kW±12.0 ±13.8 ±12.0 ±13.8 ±11.5 ±13.5 V
R
L
≥ 600 W±10 ±11.5 ±10 ±11.5 ±10 ±11.5 V
Slew Rate SR R
L
≥ 2k W
4
11 17 11 17 11 17 V/ms
Gain Bandwidth
Product GBW f
O
= 10 kHz
4
45 63 45 63 45 63 MHz
f
O
= 1 MHz 40 40 40 MHz
Open-Loop
Output Resistance
R
O
V
O
= 0, I
O
= 0 70 70 70 W
Power
Consumption P
d
V
O
= 0 90 140 90 140 100 170 mW
Offset Adjustment
Range R
P
= 10 kW±4±4±4mV
NOTES
1
Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power. A/E grades guaranteed fully
warmed up.
2
Long term input offset voltage stability refers to the average trend line of V
OS
vs. Time over extended periods after the first 30 days of operation. Excluding the initial
hour of operation, changes in V
OS
during the first 30 days are typically 2.5 mV—refer to typical performance curve.
3
Sample tested.
4
Guaranteed by design.
5
See test circuit and frequency response curve for 0.1 Hz to 10 Hz tester.
6
See test circuit for current noise measurement.
7
Guaranteed by input bias current.
REV. B
–4–
OP37–SPECIFICATIONS
Electrical Characteristics
OP37A OP37C
Parameter Symbol Conditions Min Typ Max Min Typ Max Unit
Input Offset
Voltage V
OS
Note 1 10 25 30 100 mV
Average Input
Offset Drift TCV
OS
Note 2
TCV
OSN
Note 3 0.2 0.6 0.4 1.8 mV/∞C
Input Offset
Current I
OS
15 50 30 135 nA
Input Bias
Current I
B
±20 ±60 ±35 ±150 nA
Input Voltage
Range IVR ±10.3 ±11.5 ±10.2 ±11.5 V
Common Mode
Rejection Ratio CMRR V
CM
= ±10 V 108 122 94 116 dB
Power Supply
Rejection Ratio PSRR V
S
= ±4.5 V to
±18 V 2 16 4 51 mV/ V
Large-Signal
Voltage Gain A
VO
R
L
≥ 2 kW,
V
O
= ±10 V 600 1200 300 800 V/mV
Output Voltage
Swing V
O
R
L
≥ 2 kW±11.5 ±13.5 ±10.5 ±13.0 V
Electrical Characteristics
OP37E OP37F OP37C
Parameter Symbol Conditions Min Typ Max Min Typ Max Min Typ Max Unit
Input Offset
Voltage V
OS
20 50 40 140 55 220 mV
Average Input
Offset Drift TCV
OS
Note 2
TCV
OSN
Note 3 0.2 0.6 0.3 1.3 0.4 1.8 mV/∞C
Input Offset
Current I
OS
10 50 14 85 20 135 nA
Input Bias
Current I
B
±14 ±60 ±18 ±95 ±25 ±150 nA
Input Voltage
Range IVR ±10.5 ±11.8 ±10.5 ±11.8 ±10.5 ±11.8 V
Common Mode
Rejection Ratio CMRR V
CM
= ±10 V 108 122 100 119 94 116 dB
Power Supply
Rejection Ratio PSRR V
S
= ±4.5 V to
±18 V 2 15 2 16 4 32 mV/ V
Large-Signal
Voltage Gain A
VO
R
L
≥ 2 kW,
VO
= ±10 V 750 1500 700 1300 450 1000 V/mV
Output Voltage
Swing V
O
R
L
≥ 2 kW±11.7 ±13.6 ±11.4 ±13.5 ±11 ±13.3 V
NOTES
1
Input offset voltage measurements are performed by automated test equipment approximately 0.5 seconds after application of power. A/E grades guaranteed fully
warmed up.
2
The TC VOS performance is within the specifications unnulled or when nulled withRP = 8 kW to 20 kW. TC VOS is 100% tested for A/E grades, sample tested for F/G grades.
3
Guaranteed by design.
( VS = 15 V, –55C < TA < +125C, unless otherwise noted.)
(VS = 15 V, –25C < TA < +85C for OP37EZ/FZ, 0C < TA < 70C for OP37EP/FP, and –40C < TA
< +85C for OP37GP/GS/GZ, unless otherwise noted.)
REV. B
OP37
–5–
Wafer Test Limits
OP37NT OP37N OP37GT OP37G OP37GR
Parameter Symbol Conditions Limit Limit Limit Limit Limit Unit
Input Offset
Voltage V
OS
Note 1 60 35 200 60 100 mV MAX
Input Offset
Current I
OS
50 35 85 50 75 nA MAX
Input Bias
Current I
B
±60 ±40 ±95 ±55 ±80 nA MAX
Input Voltage
Range IVR ±10.3 ±11 ±10.3 ±11 ±11 V MIN
Common Mode
Rejection Ratio CMRR V
CM
= ±11 V 108 114 100 106 100 dB MIN
Power Supply
Rejection Ratio PSRR T
A
= 25∞C,
V
S
= ±4 V to
±18 V 10 10 101020mV/V MAX
T
A
= 125∞C,
V
S
= ±4.5 V to
±18 V 16 20 mV/V MAX
Large-Signal
Voltage Gain A
VO
R
L
≥ 2 kW,
V
O
= ±10 V 600 1000 500 1000 700 V/mV MIN
R
L
≥ 1 kW,
V
O
= ±10 V 800 800 V/mV MIN
Output Voltage
Swing V
O
R
L
≥ 2 kW±11.5 ±12 ±11 ±12 ±11.5 V MIN
R
L
≥ 600 kW±10 ±10 ±10 V MIN
Power
Consumption P
d
V
O
= 0 140 140 170 mW MAX
NOTES
For 25∞C characterlstics of OP37NT and OP37GT devices, see OP37N and OP37G characteristics, respectively.
Electrical tests are performed at wafer probe to the limits shown. Due to variations in assembly methods and normal yield loss, yield after packaging is not guaranteed
for standard product dice. Consult factory to negotiate specifications based on dice lot qualification through sample lot assembly and testing.
(VS = 15 V, TA = 25C for OP37N, OP37G, and OP37GR devices; TA = 125C for OP37NT and OP37GT devices,
unless otherwise noted.)
BINDING DIAGRAM
1
2
3
46
8
7
1427U
1990
1. NULL
2. (–) INPUT
3. (+) INPUT
4. V–
6. OUTPUT
7. V+
8. NULL
REV. B
OP37
–6–
Typical Electrical Characteristics
OP37NT OP37N OP37GT OP37G OP37GR
Parameter Symbol Conditions Typical Typical Typical Typical Typical Unit
Average Input
Offset Voltage
Drift TCV
OS
or Nulled or
TCV
OSN
Unnulled
R
P
= 8 kW
to 20 kW0.2 0.2 0.3 0.3 0.4 mV/∞C
Average Input
Offset Current
Drift TCI
OS
80 80 130 130 180 pA/∞C
Average Input
Bias Current
Drift TCI
B
100 100 160 160 200 pA/∞C
Input Noise
Voltage Density e
n
f
O
= 10 Hz 3.5 3.5 3.5 3.5 3.8 nV/÷Hz
f
O
= 30 Hz 3.1 3.1 3.1 3.1 3.3 nV/÷Hz
f
O
= 1000 Hz 3.0 3.0 3.0 3.0 3.2 nV/÷Hz
Input Noise
Current Density i
n
f
O
= 10 Hz 1.7 1.7 1.7 1.7 1.7 pA/÷ Hz
f
O
= 30 Hz 1.0 1.0 1.0 1.0 1.0 pA/÷ Hz
f
O
= 1000 Hz 0.4 0.4 0.4 0.4 0.4 pA/÷ Hz
Input Noise
Voltage e
n p-p
0.1 Hz to
10 Hz 0.08 0.08 0.08 0.08 0.09 mV p-p
Slew Rate SR R
L
≥ 2k W17 17 17 17 17 V/ms
Gain Bandwidth
Product GBW f
O
= 10 kHz 63 63 63 63 63 MHz
(VS = 15 V, TA = 25C, unless otherwise noted.)
REV. B –7–
OP37
FREQUENCY – Hz
GAIN – dB
100
0.01
90
80
70
60
50
0.1 1 10 100
40
30
TEST TIME OF 10sec MUST BE USED
TO LIMIT LOW FREQUENCY
(<0.1Hz) GAIN.
TPC 1. Noise-Tester Frequency
Response (0.1 Hz to 10 Hz)
BANDWIDTH – Hz
RMS VOLTAGE NOISE – V
10
100k
1
0.1
0.01
100 1k 10k
T
A
= 25C
V
S
= 15V
TPC 4. Input Wideband Voltage Noise
vs. Bandwidth (0.1 Hz to Frequency
Indicated)
TOTA L SUPPLY VOLTAGE (V+ – V–) – Volts
VOLTAG E N OISE – nV/ Hz
5
4
1010 40
20 30
3
2
T
A
= 25C
AT 10Hz
AT 1kHz
TPC 7. Voltage Noise Density vs.
Supply Voltage
FREQUENCY – Hz
10
1
T
A
= 25C
V
S
= 15V
9
8
7
6
5
4
3
2
1
10 100 1k
VOLTAG E N OISE – nV/ Hz
I/F CORNER = 2.7Hz
TPC 2. Voltage Noise Density vs.
Frequency
SOURCE RESISTANCE –
100
1
10k100 1k
TOTAL NOISE – nV/ Hz
10
TA = 25C
VS = 15V R2
R1
RS – 2R1
AT 1kHz
AT 10Hz
RESISTOR NOISE ONLY
TPC 5. Total Noise vs. Source Resistance
FREQUENCY – Hz
CURRENT NOISE – pA/ Hz
10.0
0.1
10 10k
1.0
100 1k
I/F CORNER = 140Hz
TPC 8. Current Noise Density vs.
Frequency
FREQUENCY – Hz
100
1
1
10 100 1k
VOLTAG E N OISE – nV/ Hz
10
LOW NOISE
AUDIO OP AMP
INSTRUMENTATION
RANGE TO DC
AUDIO RANGE
TO 20kHz
I/F CORNER
741
OP37
I/F CORNER
I/F CORNER =
2.7Hz
TPC 3. A Comparison of Op Amp
Voltage Noise Spectra
TEMPERATURE – C
VOLTAG E N OISE – nV/ Hz
5
–50 –25 0 25 50 75 100 125
4
3
2
1
AT 10Hz
AT 1kHz
V
S
= 15V
TPC 6. Voltage Noise Density vs.
Temperature
TOTA L SUPPLY VOLTAGE – Volts
SUPPLY CURRENT – mA
5.0
5
TA = +125C
4.0
3.0
2.0
1.0 15 25 35 45
TA = +25C
TA = –55C
TPC 9. Supply Current vs. Supply
Voltage
Typical Performance Characteristics–
REV. B
OP37
–8–
TEMPERATURE – C
OFFSET VOLTAGE – V
60
–75
40
20
0
–20
–40
–60
–50 –25 0 25 50 75 100 125 150 175
50
10
–30
–70
30
–10
–50
TRIMMING WITH
10k POT DOES
NOT CHANGE
TCVOS
OP37C
OP37B
OP37A
OP37B
OP37A
OP37A
OP37B
OP37C
TPC 10. Offset Voltage Drift of Eight
Representative Units vs. Temperature
TIME – Seconds
OPEN-LOOP GAIN – dB
30
–20
5
0
02040
60 80 100
25
20
15
10
T
A
=
25C
T
A
= 70C
DEVICE IMMERSED
IN 70C OIL BATH
THERMAL SHOCK
RESPONSE BAND
V
S
= +15V
TPC 13. Offset Voltage Change Due
to Thermal Shock
FREQUENCY – Hz
OPEN-LOOP VOLTAGE GAIN – dB
140
1
T
A
= 25C
V
S
= 15V
R
L
2k
120
100
80
60
40
20
010 10
2
10
3
10
4
10
5
10
6
10
7
10
8
TPC 16. Open-Loop Gain vs. Frequency
TIME – MONTHS
CHANGE IN OFFSET VOLTAGE – V
6
0
2
–2
–6
4
0
–2
–6
1234567
4
0
–4
6
2
–4
TPC 11. Long-Term Offset Voltage
Drift of Six Representative Units
TEMPERATURE – C
INPUT BIAS CURRENT – nA
–50
40
20
0
–25 0 25 50 75 100 125 150
50
30
10
VS = +15V
OP37A
OP37B
OP37C
TPC 14. Input Bias Current vs. Temperature
TEMPERATURE – C
SLEW RATE – V/s
–50
70
30
10
–25 0 25 50 75 100 125
80
60
20
V
S
= 15V
SLEW
M
65
25
75
55
15
PHASE MARGIN – DEG
90
85
80
75
70
65
60
55
50
45
40
GAIN-BANDWIDTH PRODUCT – MHz
F = 10kHz
GBW
TPC 17. Slew Rate, Gain Bandwidth
Product, Phase Margin vs. Temperature
TIME AFTER POWER ON – MINUTES
CHANGE IN INPUT OFFSET VOLTAGE – V
10
101 4
23
5
T
A
= 25C
V
S
= 15V
5
OP37C/G
OP37F
OP37A/E
TPC 12. Warm Up Offset Voltage Drift
TEMPERATURE – C
INPUT OFFSET CURRENT – nA
–75
50
0–50 –25 0 25 50 75 100 125
V
S
= 15V
40
30
20
10
OP37A
OP37B
OP37C
TPC 15. Input Offset Current vs.
Temperature
FREQUENCY – Hz
60
100k 1M 10M 100M
GAIN – dB
50
40
30
20
10
0
–10
T
A
= 25C
V
S
= 15V
A
V
= 5
–80
–100
–120
–140
–160
–180
–200
–220
PHASE SHIFT – Degrees
PHASE
MARGIN
= 71
TPC 18. Gain, Phase Shift vs. Frequency
REV. B –9–
OP37
TOTA L SUPPLY VOLTAGE – Volts
OPEN-LOOP GAIN – V/V
2.5
010 40
20 30
T
A
= 25C
50
2.0
1.5
1.0
0.5
0
R
L
= 2k
R
L
= 1k
TPC 19. Open-Loop Voltage Gain vs.
Supply Voltage
CAPACITIVE LOAD – pF
PERCENT OVERSHOOT
80
60
00500 2000
1000 1500
40
20 V
S
= 15V
V
IN
= 20mV
A
V
= +5 (1k, 250)
TPC 22. Small-Signal Overshoot vs.
Capacitive Load
TIME FROM OUTPUT SHORTED TO
GROUND – MINUTES
SHORT-CIRCUIT CURRENT – mA
60
01 4
23 5
50
40
30
20
10
T
A
= 25C
V
S
= 15V
I
SC
(+)
I
SC
(–)
TPC 25. Short-Circuit Current vs. Time
FREQUENCY – Hz
28
10
4
10
5
10
6
10
7
PEAK-TO-PEAK AMPLITUDE – Volts
24
20
16
12
8
4
0
T
A
= 25C
V
S
= 15V
TPC 20. Maximum Output Swing vs.
Frequency
5V 1µs
+10V
0V
–10V T
A
= 25C
V
S
= 15V
A
V
= +5 (1k, 250)
TPC 23. Large-Signal Transient
Response
FREQUENCY – Hz
CMRR – dB
140
1k
120
100
80
60
40
10k 100k 1M 10M
V
S
= 15V
T
A
= 25C
V
CM
= 10V
TPC 26. CMRR vs. Frequency
LOAD RESISTANCE –
MAXIMUM OUTPUT – Volts
18
100 1k 10k
16
14
12
10
8
6
4
2
0
–2
TA = 25C
VS = 15V
POSITIVE
SWING
NEGATIVE
SWING
TPC 21. Maximum Output Voltage
vs. Load Resistance
20mV 200ns
+50mV
0V
–50mV
TA = 25C
VS = 15V
AV = +5
(1k, 250)
TPC 24. Small-Signal Transient
Response
SUPPLY VOLTAGE – Volts
COMMON-MODE RANGE – Volts
16
05
12
8
4
0
–4
10 15 20
–8
–12
–16
T
A
= –55C
T
A
= +125C
T
A
= +25C
T
A
= +25C
T
A
= –55C
T
A
= +125C
TPC 27. Common-Mode Input Range
vs. Supply Voltage
REV. B
OP37
–10–
OP12
OP37
D.U.T.
100k
4.3k
4.7F
2k
24.3k
VOLTAG E
GAIN
= 50,000
2.2F
22F
110k
SCOPE 1
R
IN
= 1M
0.1F
10
100k
0.1F
TPC 28. Noise Test Circuit (0.1 Hz to
10 Hz)
FREQUENCY – Hz
POWER SUPPLY REJECTION RATIO – dB
140
1
T
A
= 25C
120
100
80
60
40
20
010 100 1k 10k 100k 1M 10M 100M
160
POSITIVE
SWING
NEGATIVE
SWING
TPC 31. PSRR vs. Frequency
1 SEC/DIV
TPC 29. Low-Frequency Noise
LOAD RESISTANCE –
19
100 1k 10k 100k
SLEW RATE – V/V
T
A
= 25C
V
S
= 15V
A
V
= 5
V
O
= 20V p-p
18
17
16
15
TPC 32. Slew Rate vs. Load
LOAD RESISTANCE –
2.4
100 1k 10k 100k
OPEN-LOOP VOLTAGE GAIN – V/V
T
A
= 25C
V
S
= 15V
2.2
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
TPC 30. Open-Loop Voltage Gain vs.
Load Resistance
SUPPLY VOLTAGE – Volts
VOLTAG E N OISE – V/s
20
3
15
10
5
0
T
A
= 25C
A
VCL
= 5
6912 15 18 21
FAL L
RISE
TPC 33. Slew Rate vs. Supply Voltage
REV. B
OP37
–11–
APPLICATIONS INFORMATION
OP37 Series units may be inserted directly into 725 and OP07
sockets with or without removal of external compensation or
nulling components. Additionally, the OP37 may be fitted to
unnulled 741type sockets; however, if
conventional 741 nulling
circuitry is in use, it should be modified
or removed to ensure
correct OP37 operation. OP37 offset voltage may be nulled to
zero (or other desired setting) using a potentiometer (see figure 1).
The OP37 provides stable operation with load capacitances of
up to 1000 pF and ±10 V swings; larger capacitances should be
decoupled with a 50 W resistor inside the feedback loop. Closed
loop gain must be at least five. For closed loop gain between five
to ten, the designer should consider both the OP27 and the OP37.
For gains above ten, the OP37 has a clear advantage over the
unity stable OP27.
Thermoelectric voltages generated by dissimilar metals at the input
terminal contacts can degrade the drift performance. Best
operation will be obtained when both input contacts are main-
tained at the same temperature.
10k RP
OP37
V+
OUTPUT
V–
+
–
Figure 1. Offset Nulling Circuit
Offset Voltage Adjustment
The input offset voltage of the OP37 is trimmed at wafer level.
However, if further adjustment of V
OS
is necessary, a 10 kW trim
potentiometer may be used. TCV
OS
is not degraded (see offset
nulling circuit). Other potentiometer values from 1 kW to 1 MW
can be used with a slight degradation (0.1 mV/∞C to 0.2 mV/∞C) of
TCV
OS
. Trimming to a value other than zero creates a drift of
approximately (V
OS
/300) mV/∞C. For example, the change in TCV
OS
will be 0.33 mV/∞C if V
OS
is adjusted to 100 mV. The offset voltage
adjustment range with a 10 kW potentiometer is ±4 mV. If smaller
adjustment range is required, the nulling sensitivity can be reduced
by using a smaller pot in conjunction with fixed resistors. For
example, the network shown in figure 2 will have a ±280 mV ad-
justment range.
184.7k4.7k1k POT
V+
Figure 2. Offset Voltage Adjustment
OP37
–18V
+18V
Figure 3. Burn-In Circuit
Noise Measurements
To measure the 80 nV peak-to-peak noise specification of the
OP37 in the 0.1 Hz to 10 Hz range, the following precautions
must be observed:
∑The device has to be warmed-up for at least five minutes. As
shown in the warm-up drift curve, the offset voltage typically
changes 4 mV due to increasing chip temperature after power up.
In the ten second measurement interval, these temperature-
induced effects can exceed tens of nanovolts.
∑For similar reasons, the device has to be well-shielded from
air currents. Shielding minimizes thermocouple effects.
∑Sudden motion in the vicinity of the device can also
“feedthrough” to increase the observed noise.
∑The test time to measure 0.1 Hz to l0 Hz noise should not
exceed 10 seconds. As shown in the noise-tester frequency
response curve, the 0.1 Hz corner is defined by only one zero.
The test time of ten seconds acts as an additional zero to eliminate
noise contributions from the frequency band below 0.1 Hz.
∑A noise-voltage-density test is recommended when measuring
noise on a large number of units. A 10 Hz noise-voltage-density
measurement will correlate well with a 0.1 Hz-to-10 Hz peak-to-peak
noise reading, since both results are determined by the white
noise and the location of the 1/f corner frequency.
Optimizing Linearity
Best linearity will be obtained by designing for the minimum
output current required for the application. High gain and
excellent linearity can be achieved by operating the op amp with
a peak output current of less than ±10 mA.
Instrumentation Amplifier
A three-op-amp instrumentation amplifier, shown in figure 4,
provides high gain and
wide bandwidth. The input noise of the
circuit below is 4.9 nV/÷Hz.
The gain of the input stage is set at
25 and the gain of the second
stage is 40; overall gain is 1000.
The amplifier bandwidth of 800 kHz is extraordinarily good for
a precision instrumentation amplifier. Set to a gain of 1000, this
yields a
gain bandwidth product of 800 MHz. The full-power
bandwidth
for a 20 V p-p output is 250 kHz. Potentiometer
R7 provides quadrature
trimming to optimize the instrumentation
amplifier’s ac common-
mode rejection.
R7
100k
C1
100pF
R1
5k
0.1%
R3
390
R2
100
R4
5k
0.1%
INPUT (+)
INPUT (–)
R5
500
0.1%
R6
500
0.1%
R8
20k
0.1%
R9
19.8k
R10
500
V
OUT
NOTES:
TRIM R2 FOR A
VCL
= 1000
TRIM R10 FOR dc CMRR
TRIM R7 FOR MINIMUM V
OUT
AT V
CM
= 20V p-p, 10kHz
+
–
OP37
+
–
OP37
+
–
OP37
Figure 4a. Instrumentation Amplifier
REV. B
OP37
–12–
FREQUENCY – Hz
140
10
CMRR – dB
100 1k 10k 100k 1M
120
100
80
60
40
T
A
= 25C
V
S
= 15V
V
CM
= 20V p-p
AC TRIM @ 10kHz
R
S
= 0
R
S
= 100,
1k UNBALANCED
R
S
= 1k
BALANCED
R
S
= 0
Figure 4b. CMRR vs. Frequency
Comments on Noise
The OP37 is a very low-noise monolithic op amp. The outstanding
input voltage noise characteristics of the OP37 are achieved
mainly by operating the input stage at a high quiescent current.
The input bias and offset currents, which would normally increase,
are held to reasonable values by the input bias current cancellation
circuit. The OP37A/E has I
B
and I
OS
of only ±40 nA and 35 nA
respectively at 25∞C. This is particularly important when the input
has a high source resistance. In addition, many audio amplifier
designers prefer to use direct coupling. The high I
B
. TCV
OS
of
previous designs have made direct coupling difficult, if not
impossible, to use.
R
S
– SOURCE RESISTANCE –
10
50 10k
TOTAL NOISE – nV/ Hz
5
500 1k 5k
1
100
50
100 50k
R
S1
R
S2
1 R
S
UNMATCHED
e.g. R
S
= R
S1
= 10k, R
S2
= 0
2 R
S
MATCHED
e.g. R
S
= 10k, R
S1
= R
S2
= 5k
OP07
5534
OP27/37
REGISTER
NOISE ONLY
OP08/108
1
2
Figure 5. Noise vs. Resistance (Including Resistor Noise
@ 1000 Hz)
Voltage noise is inversely proportional to the square-root of bias
current, but current noise is proportional to the square-root of
bias current. The OP37’s noise advantage disappears when high
source-resistors are used. Figures 5, 6, and 7 compare OP-37
observed total noise with the noise performance of other devices
in different circuit applications.
Total noise = [( Voltage noise)2 + (current noise ⫻ RS)2 +
(resistor noise_]1/2
Figure 5 shows noise versus source resistance at 1000 Hz. The
same plot applies to wideband noise. To use this plot, just multiply
the vertical scale by the square-root of the bandwidth.
RS – SOURCE RESISTANCE –
100
50 10k
p-p NOISE – nV
50
500 1k 5k
10
1k
500
100 50k
RS1
RS2
1 RS UNMATCHED
e.g. RS = RS1 = 10k, R S2 = 0
2 RS MATCHED
e.g. RS = 10k, R S1 = RS2 = 5k
OP07
5534
OP27/37
REGISTER
NOISE ONLY
OP08/108
1
2
Figure 6. Peak-to-Peak Noise (0.1 Hz to 10 Hz) vs. Source
Resistance (Includes Resistor Noise)
At R
S
< 1 kW key the OP37’s low voltage noise is maintained.
With R
S
< 1 kW, total noise increases, but is dominated by the
resistor noise rather than current or voltage noise. It is only
beyond Rs of 20 kW that current noise starts to dominate. The
argument can be made that current noise is not important for
applications with low to-moderate source resistances.
The
crossover
between the OP37 and OP07 and OP08 noise occurs
in the 15 kW to 40 kW region.
R
S
– SOURCE RESISTANCE –
10
50 10k
TOTAL NOISE – nV/ Hz
5
500 1k 5k
1
100
50
100 50k
OP07
5534
OP27/37
REGISTER
NOISE ONLY
OP08/108
R
S1
R
S2
1 R
S
UNMATCHED
e.g. R
S
= R
S1
= 10k, R
S2
= 0
2 R
S
MATCHED
e.g. R
S
= 10k, R
S1
= R
S2
= 5k
1
2
Figure 7. Noise vs. Source resistance (Includes Resistor
Noise @ 10 Hz)
Figure 6 shows the 0.1 Hz to 10 Hz peak-to-peak noise. Here
the picture is less favorable; resistor noise is negligible, current
noise becomes important because it is inversely proportional to
the square-root of frequency. The crossover with the OP07
occurs in the 3 kW to 5 kW range depending on whether bal-
anced or unbalanced source resistors are used (at 3 kW the I
B
.
I
OS
error also can be three times the V
OS
spec.).
Therefore, for low-frequency applications, the OP07 is better
than the OP27/37 when Rs > 3 kW. The only exception is when
gain error is important. Figure 7 illustrates the 10 Hz noise. As
expected, the results are between the previous two figures.
For reference, typical source resistances of some signal sources
are listed in Table I.
REV. B
OP37
–13–
Table I.
Source
Device Impedance Comments
Straln Gauge <500 WTypically used in low-
frequency
applications.
Magnetic <1500 W
Low I
B
very important to reduce
Tapehead
set-magnetization problems when
direct coupling is used. OP37
I
B
can be neglected.
Magnetic <1500 WSimilar need for low I
B
in direct
Phonograph
coupled applications. OP37 will not
Cartridges
introduce any self-magnetization
problem.
Linear Variable <1500 WUsed in rugged servo-feedback
Differential
applications. Bandwidth of interest
Transformer is 400 Hz to 5 kHz.
Audio Applications
The following applications information has been abstracted from
a PMI article in the 12/20/80 issue of Electronic Design magazine
and updated.
Ca
150pF
A1
OP27
Ra
47.5k
R1
97.6k
MOVING MAGNET
CARTRIDGE INPUT
R2
7.87k
R3
100
C1
0.03F
C2
0.01F
C3
0.47F
R4
75k
++
C4 (2)
220F
LF ROLLOFF
OUT IN
OUTPUT
R5
100k
G = 1kHz GAIN
= 0.101 ( )
R1
R3
1 +
= 98.677 (39.9dB) AS SHOWN
Figure 8. Phono Pre-Amplifier Circuit
Figure 8 is an example of a phono pre-amplifier circuit using the
OP27 for A1; R1-R2-C1-C2 form a very accurate RIAA net-
work
with standard component values. The popular method to
accomplish
RIAA phono equalization is to employ frequency-
dependent feedback around a high-quality gain block. Properly
chosen, an RC network can provide the three necessary time
constants of
3180 ms, 318 ms, and 75 ms.
1
For initial equalization accuracy and stability, precision metal-
film resistors and film capacitors of polystyrene or polypropylene
are recommended since they have low voltage coefficients,
dissipation factors, and dielectric absorption.
4
(High-K ceramic
capacitors should be avoided here, though low-K ceramics—
such as NPO types, which have excellent dissipation factors,
and somewhat lower dielectric absorption—can be considered
for small values or where space is at a premium.)
The OP37 brings a 3.2 nV/÷Hz voltage noise and 0.45 pA/÷Hz
current noise to this circuit. To minimize noise from other sources,
R3 is set to a value of 100 W, which generates a voltage noise of
1.3 nV/÷Hz. The noise increases the 3.2 nV/÷Hz of the amplifier
by only 0.7 dB. With a 1 kW source, the circuit noise measures
63 dB below a 1 mV reference level, unweighted, in a 20 kHz
noise bandwidth.
Gain (G) of the circuit at 1 kHz can be calculated by the expression:
GR
R
=+
Ê
Ë
Áˆ
¯
˜
0 101 1
1
3
.
For the values shown, the gain is just under 100 (or 40 dB).
Lower gains can be accommodated by increasing R3, but gains
higher than 40 dB will show more equalization errors because of
the 8 MHz gain bandwidth of the OP27.
This circuit is capable of very low distortion over its entire range,
generally below 0.01% at levels up to 7 V rms. At 3 V output
levels,
it will produce less than 0.03% total harmonic distortion
at frequencies up to 20 kHz.
Capacitor C3 and resistor R4 form a simple –6 dB per octave
rumble filter, with a corner at 22 Hz. As an option, the switch
selected shunt capacitor C4, a nonpolarized electrolytic, bypasses
the low-frequency rolloff. Placing the rumble filter’s high-pass
action after the preamp has the desirable result of discriminating
against the RIAA amplified low frequency noise components
and pickup-produced low-frequency disturbances.
A preamplifier for NAB tape playback is similar to an RIAA
phono preamp, though more gain is typically demanded, along
with equalization requiring a heavy low-frequency boost. The
circuit In Figure 8 can be readily modified for tape use, as
shown by Figure 9.
Ca
Ra
R1
33k
TAPE
HEAD
0.47F
0.01F
R2
5k
100k
15k
T1 = 3180s
T2 = 50s
OP37
+
–
Figure 9. Tape-Head Preamplifier
While the tape-equalization requirement has a flat high frequency
gain above 3 kHz (t
2
= 50 ms), the amplifier need not be stabilized
for unity gain. The decompensated OP37 provides a greater
bandwidth and slew rate. For many applications, the idealized
time constants shown may require trimming of Ra and R2 to
optimize frequency response for non ideal tape head perfor-
mance and other factors.
5
The network values of the configuration yield a 50 dB gain at 1 kHz,
and the dc gain is greater than 70 dB. Thus, the worst-case
out-
put
offset is just over 500 mV. A single 0.47 mF output capacitor
can
block this level without affecting the dynamic range.
The tape head can be coupled directly to the amplifier input,
since the worst-case bias current of 85 nA with a 400 mH, 100 min.
head (such as the PRB2H7K) will not be troublesome.
One potential tape-head problem is presented by amplifier bias-
current transients which can magnetize a head. The OP27 and
REV. B
OP37
–14–
OP37 are free of bias-current transients upon power up or power
down. However, it is always advantageous to control the speed
of power supply rise and fall, to eliminate transients.
In addition, the dc resistance of the head should be carefully
controlled, and preferably below 1 kW. For this configuration,
the bias-current induced offset voltage can be greater than the
170 pV maximum offset if the head resistance is not sufficiently
controlled.
A simple, but effective, fixed-gain transformerless microphone
preamp (Figure 10) amplifies differential signals from low imped-
ance microphones by 50 dB, and has an input impedance of 2 kW.
Because of the high working gain of the circuit, an OP37 helps
to preserve bandwidth, which will be 110 kHz. As the OP37 is a
decompensated device (minimum stable gain of 5), a dummy
resistor, R
P
, may be necessary, if the microphone is to be
unplugged. Otherwise the 100% feedback from the open input
may cause the amplifier to oscillate.
OP37
+
–
R3
316k
Rp
30k
R1
1k
R4
316k
R2
1k
R7
10k
R6
100
OUTPUT
R3
R1
R4
R2
=
LOW IMPEDANCE
MICROPHONE INPUT
(Z = 50 TO 200 )
C1
5F
Figure 10. Fixed Gain Transformerless Microphone
Preamp
Common-mode input-noise rejection will depend upon the match
of the bridge-resistor ratios. Either close-tolerance (0.1%) types
should be used, or R4 should be trimmed for best CMRR. All
resistors should be metal-film types for best stability and low noise.
Noise performance of this circuit is limited more by the input
resistors R1 and R2 than by the op amp, as R1 and R2 each
generate a 4 nV/÷Hz noise, while the op amp generates a 3.2 nV/
÷Hz
noise. The rms sum of these predominant noise sources will
be about 6 nV/÷Hz, equivalent to 0.9 mV in a 20 kHz noise band-
width,
or nearly 61 dB below a l mV input signal. Measurements
confirm
this predicted performance.
For applications demanding appreciably lower noise, a high quality
microphone-transformer-coupled preamp (Figure 11) incorporates
the internally compensated. T1 is a JE-115K-E 150 W/15 kW
transformer which provides an optimum source resistance for
the OP27 device. The circuit has an overall gain of 40 dB, the
product of the transformer’s voltage setup and the op amp’s
voltage gain.
Gain may be trimmed to other levels, if desired, by adjusting R2
or R1. Because of the low offset voltage of the OP27, the output
offset of this circuit will be very low, 1.7 mV or less, for a 40 dB
gain. The typical output blocking capacitor can be eliminated in
such cases, but is desirable for higher gains to eliminate switching
transients.
A1
OP27
R3
100
R1
121
R2
1100
C2
1800pF
OUTPUT
150
SOURCE
T1*
T1 – JENSEN JE – 115K – E
JENSEN TRANSFORMERS
10735 BURBANK BLVD.
N. HOLLYWOOD, CA 91601
*
Figure 11. Microphone Transformer Coupled Preamp
Capacitor C2 and resistor R2 form a 2 ms time constant in this
circuit, as recommended for optimum transient response by
the
transformer manufacturer. With C2 in use, A1 must have
unity-gain
stability. For situations where the 2 ms time con-
stant is not necessary, C2 can be deleted, allowing the faster
OP37 to be employed.
Some comment on noise is appropriate to understand the
capability of this circuit. A 150 W resistor and R1 and R2 gain
resistors connected to a noiseless amplifier will generate 220 nV
of noise in a 20 kHz bandwidth, or 73 dB below a 1 mV reference
level. Any practical amplifier can only approach this noise level;
it can never exceed it. With the OP27 and T1 specified,
the
additional noise degradation will be close to 3.6 dB (or –69.5
referenced to 1 mV).
References
1. Lipshitz, S.P, “On RIAA Equalization Networks,” JAES, Vol. 27, June 1979,
p. 458-4S1.
2. Jung, W.G., IC Op Amp Cookbook, 2nd Ed., H.W. Sams and Company,
1980.
3. Jung, W.G., Audio /C Op Amp Applications, 2nd Ed., H.W. Sams and Com-
pany, 1978.
4. Jung, W.G., and Marsh, R.M., “Picking Capacitors.” Audio, February &
March, 1980.
5. Otala, M., “Feedback-Generated Phase Nonlinearity in Audio Amplifiers,”
London AES Convention, March 1980, preprint 197B.
6. Stout, D.F., and Kaufman, M., Handbook of Operational Amplifier Circuit
Design, New York, McGraw Hill, 1976.
REV. B
OP37
–15–
OUTLINE DIMENSIONS
8-Lead Ceramic DIP – Glass Hermetic Seal [CERDIP]
(Q-8)
Dimensions shown in inches and (millimeters)
14
85
0.310 (7.87)
0.220 (5.59)
PIN 1
0.005 (0.13)
MIN
0.055 (1.40)
MAX
0.100 (2.54) BSC
15
0
0.320 (8.13)
0.290 (7.37)
0.015 (0.38)
0.008 (0.20)
SEATING
PLANE
0.200 (5.08)
MAX
0.405 (10.29) MAX
0.150 (3.81)
MIN
0.200 (5.08)
0.125 (3.18)
0.023 (0.58)
0.014 (0.36) 0.070 (1.78)
0.030 (0.76)
0.060 (1.52)
0.015 (0.38)
CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETERS DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
8-Lead Plastic Dual-in-Line Package [PDIP]
(N-8)
Dimensions shown in inches and (millimeters)
SEATING
PLANE
0.015
(0.38)
MIN
0.180
(4.57)
MAX
0.150 (3.81)
0.130 (3.30)
0.110 (2.79) 0.060 (1.52)
0.050 (1.27)
0.045 (1.14)
8
14
5
0.295 (7.49)
0.285 (7.24)
0.275 (6.98)
0.100 (2.54)
BSC
0.375 (9.53)
0.365 (9.27)
0.355 (9.02)
0.150 (3.81)
0.135 (3.43)
0.120 (3.05)
0.015 (0.38)
0.010 (0.25)
0.008 (0.20)
0.325 (8.26)
0.310 (7.87)
0.300 (7.62)
0.022 (0.56)
0.018 (0.46)
0.014 (0.36)
CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
COMPLIANT TO JEDEC STANDARDS MO-095AA
8-Lead Standard Small Outline Package [SOIC]
Narrow Body
(RN-8)
Dimensions shown in millimeters and (inches)
0.25 (0.0098)
0.19 (0.0075)
1.27 (0.0500)
0.41 (0.0160)
0.50 (0.0196)
0.25 (0.0099) 45
8
0
1.75 (0.0688)
1.35 (0.0532)
SEATING
PLANE
0.25 (0.0098)
0.10 (0.0040)
85
41
5.00 (0.1968)
4.80 (0.1890)
4.00 (0.1574)
3.80 (0.1497)
1.27 (0.0500)
BSC
6.20 (0.2440)
5.80 (0.2284)
0.51 (0.0201)
0.33 (0.0130)
COPLANARITY
0.10
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
COMPLIANT TO JEDEC STANDARDS MS-012AA
REV. B
–16–
C00319–0–12/02(B)
PRINTED IN U.S.A.
Revision History
Location Page
12/02–Data Sheet changed from REV. A to REV. B.
Edits to BINDING DIAGRAM . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5
Edits to Caption for TPC 31 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10
Edits to APPLICATIONS INFORMATION Section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Added Caption to Figure 2 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Added Caption to Figures 4a and 4b . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Added Caption to Figures 8–11 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
2/02–Data Sheet changed from REV. 0 to REV. A.
Edits to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to ORDERING INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to PIN CONNECTIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
Edits to PACKAGE TYPE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
Edits to ELECTRICAL CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3
Edits to APPLICATIONS INFORMATION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8
OP37
